Continuous-wave radar system for detecting ferrous and non-ferrous metals in saltwater environments

ABSTRACT

The present invention includes systems and methods for a continuous-wave (CW) radar system for detecting, geolocating, identifying, discriminating between, and mapping ferrous and non-ferrous metals in brackish and saltwater environments. The CW radar system generates multiple extremely low frequency (ELF) electromagnetic waves simultaneously and uses said waves to detect, locate, and classify objects of interest. These objects include all types of ferrous and non-ferrous metals, as well as changing material boundary layers (e.g., soil to water, sand to mud, rock to organic materials, water to air, etc.). The CW radar system is operable to detect objects of interest in near real time.

CROSS REFERENCES TO RELATED APPLICATIONS

This application is related to and claims priority from the following U.S. patents and patent applications. This application is a continuation of U.S. patent application Ser. No. 17/830,035, filed Jun. 1, 2022, which is a continuation of U.S. patent application Ser. No. 17/498,420, filed Oct. 11, 2021, which is a continuation of U.S. patent application Ser. No. 17/033,046, filed Sep. 25, 2020, which claims priority from U.S. Provisional Patent Application No. 62/978,021, filed Feb. 18, 2020, each of which is incorporated herein by reference in its entirety.

BACKGROUND OF THE INVENTION 1. Field of the Invention

The present invention relates to continuous-wave radar systems and more specifically to detecting ferrous and non-ferrous metals in saltwater environments.

2. Description of the Prior Art

It is generally known in the prior art to provide devices capable of propagating electromagnetic waves through bodies of water, including seawater and brackish water.

Prior art patent documents include the following:

U.S. Patent Pub. No. 2016/0266246 for A system for monitoring a maritime environment by inventor Hjelmstad, filed Oct. 23, 2014 and published Sep. 15, 2016, is directed to a system for monitoring a maritime environment, the system including a plurality of detection devices for detecting objects in the maritime environment, the detection devices being configured for object detection according to different object detection schemes, and a data processing device having a communication interface and a processor, wherein the communication interface is configured to receive detection signals from the detection devices, and wherein the processor is configured to determine locations of the objects in the maritime environment upon the basis of the received detection signals within a common coordinate system.

U.S. Patent Pub. No. 2013/0278439 for Communication between a sensor and a processing unit of a metal detector by inventors Stamatescu, et al., filed Jun. 20, 2013 and published Oct. 24, 2013, is directed to a method for improving a performance of a metal detector, including: generating a transmit signal; generating a transmit magnetic field based on the transmit signal for transmission using a magnetic field transmitter; sending a receive signal based on a receive magnetic field received by a magnetic field receiver to a processing unit of the metal detector; sending a communication signal, including information from a sensor, to the processing unit; and processing the receive signal with the communication signal to produce an indicator output signal indicating a presence of a target under an influence of the transmit magnetic field; wherein one or more characteristics of the communication signal are selected based on the transmit signal to reduce or avoid an interference of the communication signal to the receive signal.

U.S. Pat. No. 8,604,986 for Device for propagation of electromagnetic waves through water by inventor Lucas, filed May 14, 2009 and issued Dec. 10, 2013, is directed to an invention concerning a device for propagating electromagnetic waves through impure water such as seawater or brackish water. The device comprises a body of polar material, for example pure water, contained in an enclosure, and an antenna arranged to emit an electromagnetic signal into the polar material. Excitation of dipoles in the polar material by the electromagnetic signal causes them to re-radiate the signal, which is thereby emitted into and relatively efficiently propagated through the water in which the device is submerged. The device offers the possibility of improved underwater communication.

U.S. Patent Pub. No. 2018/0267140 for High spatial resolution 3D radar based on a single sensor by inventors Corcos, et al., filed Mar. 20, 2017 and published Sep. 20, 2018, is directed to a novel system that allows for 3D radar detection that simultaneously captures the lateral and depth features of a target is disclosed. This system uses only a single transceiver, a set of delay-lines, and a passive antenna array, all without requiring mechanical rotation. By using the delay lines, a set of beat frequencies corresponding to the target presence can be generated in continuous wave radar systems. Likewise, in pulsed radar systems, the delays also allow the system to determine the 3D aspects of the target(s). Compared to existing solutions, the system allows for the implementation of simple, reliable, and power efficient 3D radars.

U.S. Patent Pub. No. 2002/0093338 for Method and apparatus for distinguishing metal objects employing multiple frequency interrogation by inventor Rowan, filed Feb. 11, 2002 and published Jul. 18, 2002, is directed to a method and apparatus for distinguishing metal objects employing multiple frequency interrogation. In one aspect, the method includes interrogating a target with at least two frequencies, obtaining respective response signals for the two frequencies, resolving the response signals into at least respective resistive component portions, comparing the magnitudes of at least two of the resistive component portions, selecting one response signal from among the response signals based on the comparison, and characterizing the target with the selected response signal. In other aspects, the method includes obtaining response data by interrogating the target at at least two frequencies, normalizing the response data and comparing the normalized response data. A signal is provided indicating the extent of any disagreement in the normalized response data.

U.S. Patent Pub. No. 2014/0012505 for Multiple-component electromagnetic prospecting apparatus and method of use thereof by inventor Smith, filed Mar. 27, 2012 and published Jan. 9, 2014, is directed to systems and methods for the detection of conductive bodies using three-component electric or magnetic dipole transmitters. The fields from multiple transmitters can be combined to enhance fields at specific locations and in specific orientation. A one- two- or three-component receiver or receiver array is provided for detecting the secondary field radiated by a conductive body. The data from multiple receivers can be combined to enhance the response at a specific sensing location with a specific orientation. Another method is provided in which a three-component transmitter and receiver are separated by an arbitrary distance, and where the position and orientation of the receiver relative to the transmitter are calculated, allowing the response of a highly conductive body to be detected.

U.S. Pat. No. 10,101,438 for Noise mitigation in radar systems by inventors Subburaj, et al., filed Apr. 15, 2015 and issued Oct. 16, 2018, is directed to a noise-mitigated continuous-wave frequency-modulated radar including, for example, a transmitter for generating a radar signal, a receiver for receiving a reflected radar signal and comprising a mixer for generating a baseband signal in response to the received radar signal and in response to a local oscillator (LO) signal, and a signal shifter coupled to at least one of the transmitter, LO input of the mixer in the receiver and the baseband signal generated by the mixer. The impact of amplitude noise or phase noise associated with interferers, namely, for example, strong reflections from nearby objects, and electromagnetic coupling from transmit antenna to receive antenna, on the detection of other surrounding objects is reduced by configuring the signal shifter in response to an interferer frequency and phase offset.

U.S. Pat. No. 7,755,360 for Portable locator system with jamming reduction by inventor Martin, filed Apr. 21, 2008 and issued Jul. 13, 2010, is directed to a portable self-standing electromagnetic (EM) field sensing locator system with attachments for finding and mapping buried objects such as utilities and with intuitive graphical user interface (GUI) displays. Accessories include a ground penetrating radar (GPR) system with a rotating Tx/Rx antenna assembly, a leak detection system, a multi-probe voltage mapping system, a man-portable laser-range finder system with embedded dipole beacon and other detachable accessory sensor systems are accepted for attachment to the locator system for simultaneous operation in cooperation with the basic locator system. The integration of the locator system with one or more additional devices, such as fault-finding, geophones and conductance sensors, facilitates the rapid detection and localization of many different types of buried objects.

U.S. Pat. No. 8,237,560 for Real-time rectangular-wave transmitting metal detector platform with user selectable transmission and reception properties by inventor Candy, filed Oct. 11, 2011 and issued Aug. 7, 2012, is directed to a highly flexible real-time metal detector platform which has a detection capability for different targets and applications, where the operator is able to alter synchronous demodulation multiplication functions to select different types or mixtures of different types to be applied to different synchronous demodulators, and also different waveforms of the said synchronous demodulation multiplication functions; examples of the different types being time-domain, square-wave, sine-wave or receive signal weighted synchronous demodulation multiplication functions. The operator can alter the fundamental frequency of the repeating switched rectangular-wave voltage sequence, and an operator may alter the waveform of the repeating switched rectangular-wave voltage sequence and corresponding synchronous demodulation multiplication functions.

U.S. Patent Pub. No. 2005/0212520 for Subsurface electromagnetic measurements using cross-magnetic dipoles by inventors Homan, et al., filed Mar. 29, 2004 and published Sep. 29, 2005, is directed to sensor assemblies including transmitter and receiver antennas to respectively transmit or receive electromagnetic energy. The sensor assemblies are disposed in downhole tools adapted for subsurface disposal. The receiver is disposed at a distance less than six inches (15 cm) from the transmitter on the sensor body. The sensor transmitter or receiver includes an antenna with its axis tilted with respect to the axis of the downhole tool. A sensor includes a tri-axial system of antennas. Another sensor includes a cross-dipole antenna system.

U.S. Patent Pub. No. 2017/0307670 for Systems and methods for locating and/or mapping buried utilities using vehicle-mounted locating devices by inventor Olsson, filed Apr. 25, 2017 and published Oct. 26, 2017, is directed to systems and methods for locating and/or mapping buried utilities. The publication discloses one or more magnetic field sensing locating devices include antenna node(s) to sense magnetic field signals emitted from a buried utility and a processing unit to receive the sensed magnetic field signals may be mounted on a vehicle. The received magnetic field signals may be processed in conjunction with sensed vehicle velocity data to determine information associated with location of the buried utility such as depth and position.

U.S. Patent Pub. No. 2011/0136444 for Transmit and receive antenna by inventor Rhodes, et al., filed Dec. 9, 2009 and published Jun. 9, 2011, is directed to a transmit/receive antenna for transmission and reception of electromagnetic signals. The transmit/receive antenna comprises a TX section and an RX section, where the TX section comprises a magnetically coupled TX element and a TX input terminal and the RX section comprises at least one magnetically coupled RX element and has an RX output terminal. Axes of the TX loop element and the at least one magnetically coupled RX solenoid element are parallel. Moreover, the at least one magnetically coupled RX element is positioned to provide high isolation at the RX terminal of the antenna from TX electrical signals fed to the TX input. Specifically, the at least one magnetically coupled RX element is positioned at a so that the net magnetic flux generated by the TX loop element and threading the RX solenoid element is zero.

U.S. Patent Pub. No. 2008/0224704 for Apparatus and method for detecting and identifying ferrous and non-ferrous metals by inventor Westersten, filed Sep. 9, 2005 and published Sep. 18, 2008, is directed to a metal detector using a linear current ramp followed by an abrupt current transition to energize the transmitter coil. The constant emf imposed on the target during the current ramp permits separation of transient voltages generated in response to eddy currents in the target and its environment from the voltages arising as a result of an inductive imbalance of the coil system. The temporal separation of the various voltages makes reliable differentiation between ferrous and non-ferrous targets possible.

SUMMARY OF THE INVENTION

The present invention relates to a radar system, and particularly a continuous-wave (CW) radar system for detecting ferrous and non-ferrous metals in saltwater environments.

It is an object of this invention to provide a CW radar system for detecting ferrous and non-ferrous metals in saltwater environments, increasing radar geolocation accuracy, enabling the identification of the type of material of a target object, discriminating between ferrous and non-ferrous target objects, and mapping target objects onto a 2D and 3D coordinate system.

In one embodiment, the present invention includes a CW radar system for detecting ferrous and non-ferrous metals in saltwater environments.

In another embodiment, the present invention includes a method for using a CW radar system to detect ferrous and non-ferrous metals in saltwater environments.

In one embodiment, the present invention includes a CW radar system for geolocating ferrous and non-ferrous metals in saltwater environments.

In one embodiment, the present invention includes a CW radar system for identifying ferrous and non-ferrous metal types in saltwater environments.

In one embodiment, the present invention includes a CW radar system for discriminating between ferrous and non-ferrous metals in saltwater environments.

In one embodiment, the present invention includes a CW radar system for mapping in two dimensions (2D) and three dimensions (3D) ferrous and non-ferrous metals in saltwater environments.

These and other aspects of the present invention will become apparent to those skilled in the art after a reading of the following description of the preferred embodiment when considered with the drawings, as they support the claimed invention.

BRIEF DESCRIPTION OF THE DRAWINGS

The patent or application file contains at least one drawing executed in color. Copies of this patent or patent application publication with color drawing(s) will be provided by the Office upon request and payment of the necessary fee.

FIG. 1A illustrates a block diagram of a continuous-wave (CW) radar system according to one embodiment of the present invention.

FIG. 1B illustrates a pipe frame for a CW radar system according to another embodiment of the present invention.

FIG. 1C illustrates a CW radar system according to yet another embodiment of the present invention.

FIG. 1D illustrates the CW radar system of FIG. 1C showing the location of antennas in the piping according to another embodiment of the present invention.

FIG. 1E illustrates a side view of a CW radar system according to one embodiment of the present invention.

FIG. 1F illustrates a top view of a CW radar system according to one embodiment of the present invention.

FIG. 1G illustrates a port view of a CW radar system according to one embodiment of the present invention.

FIG. 1H illustrates a radar corner reflector used during calibration of the CW radar system according to one embodiment of the present invention.

FIG. 2 illustrates an antenna setup for Transmitter (Tx) and Receiver (Rx) antennas for a CW radar system according to one embodiment of the present invention.

FIG. 3A illustrates a cross-polarization orientation for Tx and Rx antennas according to one embodiment of the present invention.

FIG. 3B illustrates a cross-polarization orientation for Tx and Rx antennas according to another embodiment of the present invention.

FIG. 3C illustrates a cross polarization orientation for Tx and Rx antennas according to another embodiment of the present invention.

FIG. 4 illustrates an antenna setup for Tx and Rx antennas for a CW radar system according to one embodiment of the present invention.

FIG. 5 illustrates an antenna setup for Tx and Rx antennas with an indication of return length differences between Rx antennas for a CW radar system according to one embodiment of the present invention.

FIG. 6 illustrates a phase shift between Rx antennas for a CW radar system according to one embodiment of the present invention.

FIG. 7A illustrates variances in signal strength between Rx₁ and Rx₂ antennas for the Rx₁ antenna according to one embodiment of the present invention.

FIG. 7B illustrates variances in signal strength between Rx₁ and Rx₂ antennas for the Rx₂ antenna according to one embodiment of the present invention.

FIG. 7C illustrates variances in frequency using a lower frequency according to on embodiment of the present invention.

FIG. 7D illustrates variances in frequency using a Tx frequency according to one embodiment of the present invention.

FIG. 7E illustrates variances in frequency when using a higher frequency according to one embodiment of the present invention.

FIG. 8 illustrates object detection ranges for a CW radar system according to one embodiment of the present invention.

FIG. 9 illustrates a precision detector for a CW radar system according to one embodiment of the present invention.

FIG. 10 illustrates a graph indicating constructive and destructive zones associated with locating an object in a saltwater environment according to one embodiment of the present invention.

FIG. 11A illustrates a graph indicating constructive and destructive zones created by a boat and a dinghy associated with locating an object in a saltwater environment according to one embodiment of the present invention.

FIG. 11B illustrates a graph indicating the energy product for a CW radar system according to one embodiment of the present invention.

FIG. 11C illustrates a graph indicating antenna signal strength associated with constructive and destructive zones of a CW radar system according to one embodiment of the present invention.

FIG. 11D illustrates a graph indicating a fore and aft antenna energy product associated with constructive and destructive zones of a CW radar system according to one embodiment of the present invention.

FIG. 12A illustrates a three-dimensional (3D) underwater depth map indicating no objects detected by a CW radar system according to one embodiment of the present invention.

FIG. 12B illustrates a 3D underwater depth map indicating multiple objects detected by a CW radar system according to one embodiment of the present invention.

FIG. 13A illustrates a 3D underwater depth map indicating the location of objects according to one embodiment of the present invention.

FIG. 13B lists all of the labels in FIG. 13A representing different geographic locations for detected objects according to one embodiment of the present invention.

FIG. 14A illustrates a two-dimensional (2D) underwater depth map indicating location coordinates for a detected object according to one embodiment of the present invention.

FIG. 14B lists all of the labels in FIG. 14A representing different geographic locations for detected objects according to another embodiment of the present invention.

FIG. 15A illustrates a 2D underwater depth map indication location coordinates for detected objects according to another embodiment of the present invention.

FIG. 15B lists all the labels in FIG. 15A representing different geographic locations for detected objects according to one embodiment of the present invention.

FIG. 16A illustrates a surveying operation with a CW radar system according to one embodiment of the present invention.

FIG. 16B illustrates a surveying operation with a CW radar system connected to a towing vessel according to one embodiment of the present invention.

FIG. 17A illustrates a 2D underwater heatmap indicating the geolocation of detected objects according to one embodiment of the present invention.

FIG. 17B lists all of the labels in FIG. 17A representing different priority zones on a 2D underwater heatmap for a CW radar system according to one embodiment of the present invention.

FIG. 18 illustrates a 2D underwater heatmap indicating the geolocation of detected objects according to another embodiment of the present invention.

FIG. 19A illustrates a 2D underwater heatmap indicating the geolocation of detected objects according to another embodiment of the present invention.

FIG. 19B lists all of the labels in FIG. 19A representing different priority zones on a 2D underwater heatmap for a CW radar system according to one embodiment of the present invention.

FIG. 20A illustrates a 2D underwater heatmap indicating a CW radar system traveling path and the geolocation of detected objects according to another embodiment of the present invention.

FIG. 20B lists all the labels in FIG. 20A representing different geographic locations for detected objects according to one embodiment of the present invention.

FIG. 21A illustrates a 2D graph indicating a land mass and a travel route for a CW radar system according to one embodiment of the present invention.

FIG. 21B illustrates a 2D heatmap graph indicating a travel route for a CW radar system according to one embodiment of the present invention.

FIG. 22A illustrates a circuit diagram of an amplifier board for a CW radar system according to one embodiment of the present invention.

FIG. 22B illustrates a pin configuration diagram for an amplifier board for a CW radar system according to one embodiment of the present invention.

FIG. 22C illustrates a pin connection diagram for an amplifier board for a CW radar system according to one embodiment of the present invention.

FIG. 22D illustrates a pin configuration and function diagram for an amplifier board for a CW radar system according to another embodiment of the present invention.

FIG. 22E illustrates a pin configuration and function diagram for an amplifier board for a CW radar system according to another embodiment of the present invention.

FIG. 22F illustrates a chart depicting the flow of signal through an amplifier board for a CW radar system according to one embodiment of the present invention.

FIG. 23 lists a table for a primary gain stage of an amplifier board for a CW radar system according to one embodiment of the present invention.

FIG. 24 lists a table for a secondary gain stage of an amplifier board for a CW radar system according to one embodiment of the present invention.

FIG. 25 lists a table for Stage One and Stage Two gain settings for an amplifier board for a CW radar system according to one embodiment of the present invention.

FIG. 26 lists a table for gain calculations for an amplifier board for a CW radar system according to one embodiment of the present invention.

FIG. 27 lists a table for Stage One and Stage Two gain settings for an amplifier board for a CW radar system according to another embodiment of the present invention.

FIG. 28A lists a table for resistance values for an amplifier board for a CW radar system according to one embodiment of the present invention.

FIG. 28B lists a table for additional resistance values for an amplifier board for a CW radar system according to one embodiment of the present invention.

FIG. 28C lists a table for additional resistance values for an amplifier board for a CW radar system according to one embodiment of the present invention.

FIG. 29A illustrates the top of an impedance matching board for a CW radar system according to one embodiment of the present invention.

FIG. 29B illustrates the bottom of an impedance matching board for a CW radar system according to one embodiment of the present invention.

FIG. 30 illustrates a graphical user interface (GUI) for displaying objects detected by a CW radar system according to one embodiment of the present invention.

FIG. 31 illustrates a GUI for displaying objects detected by a CW radar system according to one embodiment of the present invention.

FIG. 32 illustrates a sonar GUI for a CW radar system according to one embodiment of the present invention.

FIG. 33 illustrates a travel route GUI for a CW radar system according to one embodiment of the present invention.

FIG. 34A illustrates a two-dimensional (2D) map indicating a log scale of a normalized energy product for a CW radar system with no detected targets according to one embodiment of the present invention.

FIG. 34B illustrates a 2D map indicating a log scale of a normalized energy product for a CW radar system with detected targets according to another embodiment of the present invention.

FIG. 35A illustrates a 2D density and intensity map for a CW radar system according to one embodiment of the present invention.

FIG. 35B illustrates a 2D density map for a CW radar system according to one embodiment of the present invention.

FIG. 36 illustrates a GUI for displaying energy and frequency data associated with a CW radar system according to one embodiment of the present invention.

FIG. 37 illustrates a GUI for displaying phase detail and power history data associated with a CW radar system according to one embodiment of the present invention.

FIG. 38 is a schematic diagram of a system of the present invention.

DETAILED DESCRIPTION

The present invention is generally directed to a continuous-wave (CW) radar system for detecting ferrous and non-ferrous metals in saltwater environments, as well as methods of using the CW radar system to detect ferrous and non-ferrous metals in saltwater environments.

In one embodiment, the present invention includes a CW radar system for detecting ferrous and non-ferrous metals in saltwater environments.

In another embodiment, the present invention includes a method for using a CW radar system to detect ferrous and non-ferrous metals in saltwater environments.

None of the prior art discloses the use of extremely-low frequency (ELF) electromagnetic (EM) waves in saltwater to pinpoint and/or locate ferrous and non-ferrous metals.

Current underwater detection and surveying technologies make use of magnetometers which are only able to measure magnetism in ferrous materials, such as iron or steel. Magnetometers are unable to detect non-ferrous metals such as gold, silver, copper, brass, bronze, aluminum, molybdenum, zinc, or lead. In addition, magnetometers only detect the strength, or relative change of the Earth's magnetic field at a particular location, and are strictly passive sensors. Thus, magnetometers only use the natural, surrounding magnetism of an object, relying solely on the Earth's fixed magnetic output as the transmitter (Tx). In such a system, only the magnetometer as the receiver (Rx) portion can be modified or manipulated. Moreover, magnetometers have a fixed range based on receiver sensitivity which results in a minimal detection range for ferrous-only materials.

While sub-bottom sonar, side scanning sonar, dual band metal detectors, ground penetrating radar (GPR), and pulsed-wave (PW) radar techniques are also available, these detection technologies are subject to faults and limitations that make their usage in saltwater environments impractical.

Sub-bottom sonar systems are able to penetrate the ocean floor, but cannot identify, locate, or differentiate between sedimentary material, ferrous material, and non-ferrous material. These systems can only detect “acoustic” impedance, which provides for determining changes in density from one stratigraphic layer to another stratigraphic layer of the subsurface geology. Acoustic impedance corresponds to a physical “pressure” wave (e.g., sound, physical vibrations, earthquakes, etc.), while “electrical” impedance corresponds to an electromagnetic wave (e.g., signals from radio, cell phones, microwaves, light, etc.). Typically, sub-bottom sonar systems operate in the acoustic range of 5-50 kilohertz (kHz). While lower frequencies penetrate deeper into mud and silt, these systems lack the ability to provide real detail of the detected layers. In contrast, higher frequencies provide minor surface layer detail, but lack the ability to penetrate sand, mud, or silt.

Side-scanning sonar is typically used to create a map of the ocean bottom. However, much like sub-bottom sonar, side-scanning sonar lacks the ability to penetrate into the surface of the ocean bottom. The devices utilized for side-scanning sonar are also acoustic-only devices.

Dual band metal detectors are also used in underwater salvaging. These systems are active systems and are able to identify ferrous and non-ferrous metals using dual frequency differences to determine metal types (i.e., ferrous vs. non-ferrous). Dual band metal detectors operate in the 5-100 kilohertz (kHz) range and are typically able to penetrate between 3 inches to 18 inches of sand, saltwater, soil, etc. In addition, dual band metal detectors are restricted to searching an area directly under the detector unit's coil diameter, which is typically less than 12 inches in diameter.

Ground penetrating radar (GPR) systems are used only in air environments. The frequency of GPR falls between 10-3000 megahertz (MHz). Even if a GPR system was encapsulated for ocean use, the radar energy would immediately be absorbed on contact with saltwater and its effective range would be less than an inch. High frequency, commercial, hand-held metal detectors used on the land have the ability to not only detect metal objects (typically <6 ft away), but are also able to classify what type of metal the object is made of (i.e., gold, silver, iron, etc.). This is accomplished through the differences between the multiple radar bands. In multiple signal systems, signals reflect off of the metal, but based on the metal material, the strength and phase of return between the frequencies is different. However, the frequencies of these commercial metal detectors do not transmit far enough in saltwater environments before being completely absorbed by the water and hence are operationally ineffective.

Pulsed-wave (PW) radar systems transmit electromagnetic (EM) waves during a time duration, or pulse width. During this process, the receiver is isolated from the antenna in order to protect the receiver's sensitive components from a transmitter's high-power EM waves. No received signals can be detected during this time.

The faults and limitations of the previously mentioned detection and sensor technologies have led to the present invention: a continuous-wave (CW) radar system for detecting ferrous and non-ferrous objects in saltwater environments. Such a radar system combines all of the positive attributes of current sensor and detection technologies with none of the limitations or faults. Instead of relying on “acoustic” waves, the system uses “electromagnetic” waves, but at frequencies which allow for greater penetration than even the most sophisticated sub-bottom sonar systems.

The CW radar system generates ELF electromagnetic (EM) waves and uses those waves to perform functions including, but not limited to, detection, location, and classification of objects of interest. Such objects include, but are not limited to, all types of ferrous and non-ferrous metals, as well as changing material boundary layers (e.g., soil to water, sand to mud, rock to organic materials, etc.). In one embodiment, the ELF waves used are between 100 Hz and 3000 Hz. The CW radar system is operable to detect and record all frequencies below approximately 3000 Hz. Thus, the ELF waves are operable to propagate through water, soil, sand, rock, and/or metals. A portion of the ELF waves are reflected off of thicker metals and boundary layers, which are used to perform functions including, but not limited to, detection, location, analysis, mapping, and/or classification of objects. This entire process is performed using short, manageable antennas which are operable to transmit and receive the same ELF waves or signals. Thus, the present invention is operable to identify both ferrous and non-ferrous metals.

In one embodiment, the CW radar system of the present invention makes use of a multi-band system capable of operating at simultaneous frequencies in order to decrease location error and provide the ability to specifically identify the type of metal associated with an object and/or target during operations.

A key element of this system is the environment it functions in: saltwater. Saltwater is conductive and distributed equally around the system's sensors. The saltwater becomes a barrier to transmission, due to absorption, but simultaneously acts as a filter to keep the detection ranges local to the sensor. Without a saltwater environment, the transmission ranges measure in kilometers instead of meters. All conductive surfaces within a few kilometers would create a return signal and greatly reduce the ability to locate a specific target, local to the sensors. Saltwater changes the effective wavelength from potentially thousands of kilometers to less than 100 meters, enabling detection of targets, as well as localization of objects around the system's sensors from a few meters to a few hundred meters, based on Tx signal strength and Rx sensitivity. In one embodiment, the system can handle variations in salinity within at least a 50 mile radius without further adjustment. In another embodiment, the system can be recalibrated at startup and/or when the saltwater environment changes to accommodate different levels of salinity. In one embodiment, the system is operable to detect targets and/or objects in brackish water.

The CW radar system is operable to function in deep saltwater environments, from tens of feet to tens of thousands of feet. Moreover, the design of the CW radar system of the present invention prevents saltwater from contaminating the towing device(s) connected to a collecting and/or towing vehicle. The CW radar system is capable of determining absolute object and/or target geolocation to within <4 meters (m) circular error probable (CEP) of accuracy. The CW radar system is also capable of providing object and/or target geolocation within <2 m CEP of accuracy using a relative positioning system. In one embodiment, relative positioning is determined through the use of a relative GPS receiver. In another embodiment, the relative positioning of detected targets is determined with respect to known metal targets or markers placed within the field of search.

Referring now to the drawings in general, the illustrations are for the purpose of describing one or more preferred embodiments of the invention and are not intended to limit the invention thereto.

The continuous-wave (CW) radar system of the present invention utilizes a combination of transmitter (Tx) and receiver (Rx) antennas. By using multiple Rx antennas, the system is able to localize objects.

FIG. 1A illustrates a block diagram of a continuous-wave (CW) radar system according to one embodiment of the present invention. The components include, but are not limited to, a transmitter computer, a receiver computer, at least two amplifiers, a storage component, at least two impedance matching hardware components coupled to the at least two amplifiers, a continuous wave sensor head (the submerged, towed structure comprising the Transmitter (Tx), Receiver (Rx) antennas, down plane, horizontal stabilizer, floatation elements, and structural support elements), a tow point, a Tx communications cable, a Rx communications cable. The continuous wave sensor head is comprised of at least one transmitter (Tx) antenna and at least two receiver (Rx) antennas. The submersion of the Tx and Rx antennas in a saltwater environment modifies the relative Tx and Rx wavelengths from thousands of kilometers to less than a few hundred of meters range. This enables the use of electrically short dipole antennas to collect enough energy, at the Rx antennas, to detect, locate, and/or identify all types of ferrous and non-ferrous metals.

FIG. 1B illustrates a pipe frame for a CW radar system according to another embodiment of the present invention. The CW radar system is comprised of a multitude of piping, operable to house at least one Tx antenna and at least two Rx antennas.

FIG. 1C illustrates a CW radar system according to yet another embodiment of the present invention. The CW radar system is comprised of components including, but not limited to, a tow point, a Rx/Tx communications cable, a down plane, a horizontal stabilizer, at least one Tx antenna, and/or at least two Rx antennas. The tow point is positioned to maximize the stability of the CW radar system while it is being towed from a towing vessel. In one embodiment, the towing vessel is a watercraft, including but not limited to a boat, ship, YET SKI, or submarine. In another embodiment, the towing vessel is an underwater Remotely Operated Vehicle (ROV). In another embodiment, the towing vessel is an Unmanned Underwater Vehicle (UUC). The tow point also helps keep the tow cable separate from the data cable. The data cable enters the CW radar system above and behind the tow point on top of the CW radar system. The data cable has multiple electrically shielded wires running throughout the structure to each of the six antennas, four Rx antennas and two Tx antennas. Furthermore, the path of the data cable throughout the CW radar system is also important, as the cable(s) are run in order to maximize their individual cross polarization to the Tx antennas. By positioning the Tx antennas at a 90-degree angle in relation to the Rx antennas, this prevents the Rx antenna's wiring from coming into contact with the Tx antenna output pattern, further reducing the crosstalk from the Tx antennas into the Rx antenna data cable(s). The 90-degree angle between Tx and Rx antennas also provides for the majority of the direct path attenuation through the use of the polarization properties of dipole antennas. Without this attenuation, signal from the Tx antenna would saturate the Rx antenna and any returning signal from a target would be lost due to the much, much stronger direct path signal.

FIG. 1D illustrates the CW radar system of FIG. 1C showing the location of antennas in the piping according to another embodiment of the present invention. The CW radar system is comprised of components including, but not limited to, at least two bow Rx antennas, at least two Tx antennas placed approximately at the center of the CW radar system, and at least two aft Rx antennas. In one embodiment, the at least two Tx antennas are positioned near a horizontal stabilizer for the CW radar system. In one embodiment, the Tx and Rx antennas are dipole antennas. When two dipole antennas are placed in close proximity to one another, this sets up a transformer-like condition, resulting in a loss of power to the radar system if each antenna is too close to the other. As in a transformer, energy from one Tx antenna is absorbed by any adjacent Tx antenna. This results in a direct loss of usable power and requires the system to also prevent this lost energy/power from feeding back in to either Tx antenna's circuitry. In order to minimize these effects, the CW radar system of the present invention has been constructed with a functional distance built into the structure, holding the radar antennas separate. This functional distance is a function of how much transmitted energy loss is acceptable for the CW radar system and the specific transmitted frequencies being used. In one embodiment, the range for acceptable energy loss is between 5-20%. In one embodiment, the antennas are placed between approximately 9-24 inches away from each other to maintain acceptable energy loss wherein the distance is inversely proportional to the amount of energy loss. Where the Rx antennas are also dipole antennas, the Tx antennas must be angled 90-degrees or near-90-degrees with respect to the Rx antennas in order to maximize the benefits of cross polarization. In another embodiment, the Tx and Rx antennas are short dipole antennas. In another embodiment, the Tx and Rx antennas are half-wave dipole antennas. In another embodiment, the Tx and Rx antennas are folded dipole antennas. In yet another embodiment, the Tx and Rx antennas are bow-tie dipole antennas. In yet another embodiment, the Tx and Rx antennas are cage dipole antennas. In yet another embodiment, the Tx and Rx antennas are halo dipole antennas. In yet another embodiment, the Tx and Rx antennas are turnstile dipole antennas. In yet another embodiment, the Tx and Rx antennas are sloper dipole antennas. In yet another embodiment, the Tx and Rx antennas are inverted “V” dipole antennas. In yet another embodiment, the Tx and Rx antennas are G5RV dipole antennas. In yet another embodiment, the Tx and Rx antennas are not dipole antennas.

In one embodiment, a Tx antenna is placed in one of two center pipes and the corresponding Rx antenna pair(s) are perpendicular to the Tx antenna, forward and aft. Each Rx antenna is placed approximately 1-3 meters from the Tx antenna. The Rx antenna pair(s) are always perpendicular or substantially perpendicular to the Tx antenna in order to take advantage of the noise cancellation provided by the polarization characteristics of the antennas. In one embodiment, one Tx antenna effectively has four Rx antennas, two forward and two aft, with each Rx antenna spaced approximately 1-2 meters away from the Tx antenna. In one embodiment, the Tx and Rx antennas are spaced approximately 60 inches apart from each other. In one embodiment, the Tx and Rx antenna structures are approximately 14.5 feet long in total when using a multiband system.

The addition of multiple Rx antennas facilitates the detection of signal strength and phase changes between the Rx antennas. Each Rx antenna remains perpendicular or substantially perpendicular to the surface of the water, while the Tx antenna(s) remain parallel or substantially parallel to the water's surface. This keeps the Tx and Rx antennas at right angles to each other, preventing self-jamming and shielding the Rx antennas from the water's surface reflection. Thus, this orientation functions to prevent self-jamming and reduce the surface bounce energy from the Tx into the Rx antenna(s).

In one embodiment, the CW radar system includes a third Tx/Rx antenna combination. In another embodiment, the CW radar system includes a fourth Tx/Rx antenna combination. In yet another embodiment, the CW radar system includes more than four Tx/Rx antenna combinations. In one embodiment, additional cross pipes are included in the design of the piping frame, thereby providing for the CW radar system to accommodate more bands while only increasing the overall length of the piping frame of the CW radar system for each added band. All portions/elements of the underwater structure housing the cables, Tx/Rx antennas, and connectors are made from dielectric or non-metallic, non-conducting material.

The entire CW radar system is towed from a single tow point, maximizing stability while towing and keeping the towing cable separate from a data cable. The data cable enters the CW radar system above and behind the tow point. The data cable has multiple electrically shielded wires running throughout the structure to each of the Tx and Rx antennas. Data cables are positioned to maximize their individual cross-polarization while avoiding exposure to the Tx antenna(s) output pattern, reducing crosstalk from the Tx and Rx antenna data cables.

The structure of the CW radar system of the present invention further minimizes issues with vibration. Mechanical vibrations induce a Doppler response into the processed data, directly contributing to decrease in Signal to Noise Ratio (SNR) in the system. In one embodiment, the ballast between the panels is constructed of high-density foam with a crush depth of more than 4000 feet deep. This enables the system to remain buoyant and keeps panels of the system from vibrating under towing conditions. The panels also serve to keep the pipes and structures holding the cables and antennas rigid. Thus, the combination of the panels and high-density foam reduces overall system vibration when being towed. In embodiment, the system is towed at speeds up to approximately 12 knots (kts). In another embodiment, the system is towed at a speed greater than 12 kts.

FIG. 1E illustrates a side view of a CW radar system according to one embodiment of the present invention. A tow point is positioned at one end of the CW radar system, enabling a towing vessel to attach to the CW radar system. The CW radar system also includes a buoyancy tank, enabling the CW radar system to remain afloat on the surface of a body of water. In one embodiment, the CW radar system is connected to the towing vessel via a tow cable and a data cable. In one embodiment, the CW radar system is connected to the towing vessel via a dinghy, where the dinghy is connected to the towing vessel via a data cable and tow cable, and the dinghy connects to the CW radar system using the data cable and/or tow cable.

FIG. 1F illustrates a top view of a CW radar system according to one embodiment of the present invention. The CW radar system includes at least one down plane, operable to adjust the angle of the CW radar system as it travels along the surface of a body of water, and at least one buoyancy tank.

FIG. 1G illustrates a port view of a CW radar system according to one embodiment of the present invention.

In one embodiment, the CW radar system includes a down plane. The down plane is placed forward of the center of balance of the CW radar system. This positioning, in conjunction with the two point and horizontal stabilizer, provides a balanced, smooth towing operation. The down plane is sized and angled to provide precise underwater depths for the CW radar system when being towed at peak, desired collection speeds. In one embodiment, the peak towing speed for collection is approximately 2-8 kts. The depths of the CW radar system's keel from the ocean surface are a function of tow cable length for a set collection speed. In one embodiment, the down plane is a fiberglass down plane. In one embodiment, the down plane is made of polyvinyl chloride (PVC). In another embodiment, the down plane is made of fiberglass composite. In another embodiment, the down plane is made of a non-metallic, non-conducting, dielectric material. In one embodiment, the down plane is actively adjustable. Using an actively adjustable down plane enables the CW radar system to operate at greater depths. In another embodiment, the down plane is coupled with a sonar reflector system on the CW radar system in order to precisely locate targets underwater. This coupling of the down plane with the sonar reflector system increases the geolocational accuracy of the CW radar system during surveying operations. In one embodiment, the sonar reflector is a corner reflector that reflects a sonar acoustic signal. In one embodiment, the sonar reflector signal is used by the towing vessel to determine the location and depth of the CW radar system as it is being towed. In one embodiment, the sonar reflector is operable to locate the corners of the CW radar system as it is being towed. In one embodiment, there is at least one transponder on each side of the towing vessel. The transponders each emit signals of different frequencies. The location and depth of the CW radar system is calculated using the combined stereo vision of the at least one transponder on each side of the towing vessel. In one embodiment, the system is operable to generate a 3D image of the CW radar system as it is being towed with geolocation accuracy of the CW radar system within 10 ft.

In one embodiment, the CW radar system of the present invention further includes a towed floatation device attached to the CW radar system. In one embodiment, the towed flotation device is a dinghy. The towed floatation device cushions the CW radar system against waves, reducing sudden jerking motions encountered while towing and vibrational noise. In one embodiment, the towed floatation device also carries an additional GPS receiver that helps to triangulate the location of the underwater sensor-head during surveying operations. The combination of all GPS receiver(s) on the towing vessel and the towed floatation device together provide a <1 m accuracy of the underwater sensor-head.

In addition, the overall distance between the CW radar system of the present invention and a towing vessel is of critical importance. The engines, hull structures, electronics, aluminum superstructures, screws, and other vessel or tow components can create a target that is detected by the CW radar system, even though the parts of the towing vessel/dinghy are above or below the waterline. In one embodiment, the CW radar system is towed from a vessel between approximately 200 feet (ft.) to 500 ft. behind the vessel. In one embodiment, the CW radar system is attached to a dinghy, where the distance between the towing vessel and the dinghy is between approximately 100 ft. to 300 ft. and the distance from the CW radar system and the dinghy is approximately 50 ft. to 400 ft. In another embodiment, the dinghy is more than 300 ft. away from the towing vessel and the CW radar system is more than 400 ft. from the dinghy. In one embodiment, the towing vessel is a watercraft (boat, ship, JET SKI, submarine, etc.). In one embodiment, the towing vessel is an underwater Remotely Operated Vehicle (ROV). In one embodiment, the towing vessel is an Unmanned Underwater Vehicle (UUV). In one embodiment, the dinghy is replaced with a dynamic winch system onboard the towing vessel. The depth of the sensor-head is then determined by the distance of the sensor-head behind the towing vessel. The sensor-head distance from the towing vessel is lengthened or shortened to increase or decrease the sensor-head depth.

The CW radar system is capable of transmitting multiple, simultaneous frequencies, up to approximately 5000 Hz. In one embodiment, the CW radar system is a dual-band system that operates using two separate radars in the same sensor head, enabling the transmission of multiple frequencies from multiple radars simultaneously. By using multiple frequencies, the CW radar system has increased 3-Dimensional (3D) target geolocation functionality and is operable to more efficiently classify surveyed objects and/or target materials and detect objects and/or targets through solid surfaces, the solid surfaces including but not limited to, soil, sand, reef, mud, and/or iron/steel. In one embodiment, this dual-band system is comprised of at least one Tx antenna and at least two Rx antennas. In one embodiment, this dual-band system is comprised of at least two or more Tx antennas and at least two or more Rx antennas. In one embodiment, geolocation is achieved with a set of global positioning system (GPS) coordinates. In one embodiment, geolocation is based on a differential GPS system. In one embodiment, the CW radar system uses GPS receivers on land and/or GPS receivers at anchor points in the underwater environment to improve the accuracy of the GPS geolocation using differential GPS. In one embodiment, the CW radar system includes a plurality of GPS receivers located on the towing vessel and on the towed floatation device to improve the accuracy of geolocation. In one embodiment, geolocation is based on a localized or relative coordinate system.

In one embodiment, geolocation is based on a relative coordinate system wherein the relative coordinate system is defined by metal targets and/or reflectors placed under or on the water surface and in the survey field prior to/or during survey operations. In one embodiment, the metal targets are aluminum. In one embodiment, the metal targets are rounded so as not to skew the directions of the signals that they reflect. In one embodiment, the metal targets are used for relative geolocation within 1-2 m of a target and/or object. All objects discovered from the CW radar system are then referenced relative to the metal targets and/or reflectors that were placed into the survey field. In one embodiment, geolocation is based on a relative coordinate system using active transmitters placed under or on the water surface and in the survey field prior to/or during survey operations. All objects discovered from the CW radar system are then referenced relative to the active transmitters that were placed into the survey field. In another embodiment, the GPS coordinate system is used to locate the metal targets, active transmitters, and/or reflectors used to define the relative coordinate system. In one embodiment, a combination of GPS coordinates and relative coordinates are used to geolocate the objects and/or targets in the target survey area.

By using a dual-band system, the CW radar system is able to transmit a signal from any Tx antenna. Additionally, the CW radar system is further able to transmit many signals, simultaneously, within a specific band. For example, the CW radar system is able to transmit multiple signals simultaneously within a frequency band up to approximately 5000 Hz. However, the higher the frequency used, the weaker the overall return signal strength is, assuming the same output power per frequency at the Tx.

In another example, the transmitter is able to transmit between 0.1 and 100+ watts of power. If two frequencies are transmitted from the single transmitter, each frequency will have one-quarter of the amount of power available. In this system, power is equal to voltage squared. Therefore, in order to transmit two frequencies out of one band, power is sacrificed. The CW radar system can generate multiple transmission frequencies through one of three methods. In one embodiment, the CW radar system transmits two or more frequencies simultaneously from a single Tx antenna. This embodiment reduces the number of Tx/Rx pairs in the overall system, thus reducing the overall physical complexity of the system. A single Tx antenna can transmit a few or even tens of frequencies simultaneously. The disadvantage of this approach is that the power required to transmit multiple frequencies increases as a squared function of each additional frequency. If one frequency is now expanded to two simultaneous frequencies, then the amplifier power required to match the single frequency increases from a factor of (1)²=1 to (2)²=4. In the case where the amplifier is at maximum power setting and an additional frequency is added, then signal strength is reduced effectively from a factor of 1/(1)²=1 to 1/(2)²=¼. In the case of 3 simultaneous frequencies, this transmitted power per frequency falls to 1/(3)²= 1/9 of the system's total output power.

In another embodiment, there are multiple Tx/Rx pairs in the system. In one embodiment, there is one Tx/Rx pair for each frequency transmitted. This allows the use of multiple amplifiers (one for each Tx antenna) and provides more overall power transmitted per each frequency. The current CW radar in FIG. 1D shows two separate Tx/Rx systems in the same structure. The structure shown can easily handle 3 or more Tx/Rx pairs. The advantage is that output power can be maximized. A slight disadvantage is discussed in [00128] above where some power is lost due to transformer-like losses. The amount of power lost as discussed in [00128] is much less than the amount of power lost in the first embodiment wherein multiple frequencies are transmitted from a single Tx/Rx pair.

The third embodiment is a combination of approaches 1 and 2 above to achieve the desired number of frequencies transmitted with the desired amount of power from the total amplifiers in the system. An additional issue, whether using approach one, two, or three above is that the transmission of any two frequencies will also generate a third signal wherein the frequency of the third signal is the beat frequency, or the difference between the frequencies of the two intended signals. As an example, transmitting two signals at 300 Hz and 500 Hz from either approach above will also generate a third frequency of 200 Hz (500 Hz-300 Hz). Transmitting three frequencies will produce the three frequencies and two additional beat frequencies.

With multiple frequencies being transmitted from a single band radar system or a dual band radar system transmitting two distinct frequencies, the result is that each frequency has its own set of constructive and destructive zones that differ in range based on the frequency (wavelength) of transmission, as illustrated in FIG. 8 . By using multiple, simultaneous frequencies, the CW radar system is operable to provide the exact distance to an object and/or target. As the distance between the object and/or target and the sensor head of the CW radar system changes, the signals received by the Rx antenna or antennae of the CW radar system transition between constructive and destructive interference. These transitions depend on the frequency of the transmitted signals and are used to measure overall distance between the CW radar system and an object and/or target. The use of multiple frequencies allows for the CW radar system to detect and identify an object and/or target with more detail.

In a pulsed system, distance is calculated in part from the time that it takes for a sent Tx antenna pulse to reach the Rx antenna after interacting with an object and/or target. However, with continuous wave systems, there is no measure of time because the Tx antenna is always sending out a signal. The CW radar system of the present invention solves this distance measurement issue associated with current CW radar systems by employing different frequencies with different constructive and destructive zone lengths, as illustrated in FIG. 8 . The combination of received signals of varying frequencies that have passed through respective constructive and/or destructive zones after being reflected off an object and/or target allows the CW radar system to precisely identify each return signal, as well as the location of an object and/or target as well as its composition. The CW radar system also uses the phase shift of the returning signal to compute distance, metal type, and precise location measurements.

Furthermore, the use of multiple frequencies by the CW radar system of the present invention enables the system to detect and/or penetrate steel. In the oil and gas industries, a process known as “Pigging” is used to locate a sensor inside a steel pipe. The sensor transmits a frequency low enough to penetrate a steel walled pipe. The CW radar system of the present invention is operable to create these same frequencies by either directly transmitting a frequency that is low enough to penetrate a steel-walled pipe or by transmitting two separate frequencies, wherein the beat frequency of the two separate frequencies is low enough to penetrate a steel-walled pipe. For example, if the two frequencies being transmitted from a single radar system are approximately 311 Hz and approximately 333 Hz, respectively, there is a third signal with a beat frequency also being transmitted at the difference between the two frequencies. In this example, this beat frequency is approximately 22 Hz (333 Hz-311 Hz). This third frequency value, 22 Hz, is the typical frequency used in “Pigging.” It transmits through steel and can be detected by the dipole antennas of the CW radar system of the present invention.

Cross Polarization

The CW radar system of the present invention uses cross polarization to eliminate the direct path energy from Tx to Rx antennas, which deflects any reflected energy from an object and/or target. Cross polarization using dipole antennas is accomplished through physical orientation. The Tx antenna is oriented 90 degrees from the Rx antenna(s).

FIG. 2 illustrates an antenna setup for Tx and Rx antennas for a CW radar system according to one embodiment of the present invention. The Tx antenna is positioned between two Rx antennas. In addition, the Tx antenna is placed at a 90-degree angle in relation to the two Rx antennas.

An added benefit of this embodiment is the noise cancellation provided by the polarization characteristics of the Tx and Rx antennas. In current signals, there are several primary sources of noise. Sudden movements and/or jerking on any towing device(s) creates significant noise in the signal received by the Rx antennas, with greater noise created in any forward Rx antennas. Another source of noise includes vibration. As the CW radar system moves through water, the turbulence across the structure produces a large amount of noise via vibration. Moreover, any flexing of the CW radar system during towing and/or collecting causes a Doppler effect in the signal(s).

FIG. 3A illustrates a cross-polarization orientation for Transmitter (Tx) and Receiver (Rx) antennas according to one embodiment of the present invention. The Tx antenna is placed at a 90-degree angle in relation to all Rx antennas. In one embodiment, the Tx and Rx dipole antennas are between approximately 8 to 30 inches in length and have diameters between approximately ½ to 2 inches. In a continuous radar system such as the present invention, the direct signal path from the Tx to the Rx antenna(s) is of much higher magnitude than that of the return signal that has interacted with an object and/or target. Typical radar systems used by the military and commercial communities use pulsed radar, wherein the Tx antenna sends out short, pulsed bursts of energy while the Rx antennas are turned off or electrically protected from the direct path energy to avoid the interference of the direct path energy. The Rx antennas are then turned on when the Tx antennas are turned off in order to receive only the return signal from the object and/or target. However, since the frequencies of the present invention are extremely low and the wavelengths of objects are long, pulsed radar systems will not work in the conditions where the CW radar system of the present invention is operable to function. Thus, the CW radar system uses cross polarization of the Tx and Rx antennas to eliminate the direct path energy from the Tx antenna(s) to the Rx antennas, enabling the system to detect distant targets and/or objects while the Rx antennas are located directly next to the bright and loud Tx antenna(s).

FIG. 3B illustrates a cross polarization orientation for Tx and Rx antennas according to another embodiment of the present invention. Cross polarization using dipole antennas is accomplished through physical orientation. The Tx antenna is oriented approximately 90 degrees from the Rx antennas. When using dipole antennas, multiple Tx antennas in close proximity to one another result in a transformer-like condition and loss of power will occur if the Tx antennas are too close to one another. In a transformer, energy from one Tx antenna will be absorbed by an adjacent Tx antenna such that none of the transmitted energy will propagate away from the Tx antenna. The result is a direct loss of power and a need to prevent this lost power from feeding back into the first Tx antenna's circuitry. In order to minimize these effects, the CW radar system of the present invention ensures a functional distance has been built into the structure holding the separate transmitters. This functional distance is a function of how much energy loss is acceptable and the specific signal frequencies being transmitted by the CW radar system. In one embodiment, the CW radar system of the present invention separates Tx antennas by approximately 6 inches to approximately 36 inches. Since the Rx antennas are also dipole antennas, the angle between the Tx antenna(s) and the Rx antennas is approximately 90 degrees, maximizing the benefits of cross-polarization.

FIG. 3C illustrates a cross polarization orientation for Tx and Rx antennas according to another embodiment of the present invention.

FIG. 4 illustrates an antenna setup for Tx and Rx antennas for a CW radar system according to one embodiment of the present invention. The Tx antenna is positioned between two Rx antennas. The Tx antenna is placed at a 90-degree angle in relation to the two Rx antennas.

In addition, a third source of noise is the electronic equipment powering, controlling, connected to, and/or in close proximity to the CW radar system. All electronics have noise associated with them and must be accounted for and/or corrected for. Included in the noise radiating from the electronic equipment is the issue of electronic drift. This electronic drift, or drift current, is caused by particles getting pulled by an electric field. Without noise controls, fluctuations in electronic equipment can produce around 30-60 dBW of signal, which is equivalent to approximately 1/1,000 of a Watt of signal in the Rx antenna(s). In the presence of an object and/or target, signal in the Rx antenna(s) is in a range of approximately 1/100 of a Watt to less than 1/100,000,000 of a Watt; hence, there is a need to monitor and control noise inputs to the overall system in order to accurately detect signals in the Rx antenna from an object and/or target.

Drift current, or electronics drift, is caused by electric force, i.e., charged particles get pushed by an electric field. Electrons, being negatively charged, get pushed in the opposite direction of the electric field, but the resulting conventional current points in the same direction as the electric field. The CW radar system of the present invention must account for drift current from elements including, but not limited to, temperature, vibrations, and/or system electronics. These elements have a natural drift state. If unaccounted for, excess noise is created within the system and electronic saturation from the noise will effectively overpower the target signal strength. Therefore, it is important for the CW radar system to maintain a balanced signal-to-noise ratio. The CW radar uses multiple elements to reduce or control electronic drift. The first is through DC (Direct Current) biasing control. The second is through Analog Filtering. The third is through climate control of the electronic boards/elements during operations. The electronic components are mounted in thermal electric coolers/heaters to maintain constant temperatures during operations. Environmental temperature fluctuations are maintained to less than approximately 1° Celsius (C) through a combination of heating and cooling. In one embodiment, the CW radar system is operated at a temperature range of approximately 4° C. to 16° C. to avoid thermal drift.

Additionally, several sources of signal clutter must be accounted for. These include, but are not limited to, the reflection of the transmitted signal off the surface of the water above the CW radar system and the reflection of the transmitted signal off the bottom of the ocean. Regarding the reflection off the surface of the water, if the surface was perfectly flat, energy from the Tx antenna(s) would be completely absorbed at the surface. However, the surface is almost never perfectly flat due to wave action, ocean swells, wakes caused by other objects, winds, currents, etc., which result in disturbances that create a reflection at the air-water boundary, bouncing energy towards the Rx antenna(s). This can amount to approximately 0.00001 to as much as approximately 0.01 dBW of variance in signal from the surface reflection. In one embodiment, the signal reflection off the surface of the water is most noticeable when the CW radar system is within 150 ft of the surface of the water.

The reflection off the bottom of the ocean is a second source of clutter, but much less so than the reflection off the surface of the ocean. Because sand is typically a mixture of water and rock, the boundary layer effects are minimal. In the case of reef environments, or other rock formations, the boundary layer effects are also minimal, but can also create noise components that need to be accounted for during post-processing.

Phase Shift

When using multiple Rx antennas of differing electrical path lengths in conjunction with continuous wave (CW) transmissions, a phase shift occurs in the signals between each Rx antenna. If the path lengths from the Tx transmitter antenna to the target and then to the Rx antennas for the multiple Rx antennas were identical, there would be no phase difference between the signals received by each antenna. This phase shift occurs only under a very precise set of conditions, including when multiple Rx antennas are placed perpendicular (90 degrees) or near perpendicular to the direction the system is being towed. In one embodiment, one transmitter has four receivers, two forward and two aft, with each spaced between approximately 1-3 meters away from the Tx. In another embodiment, one transmitter has two receivers, one forward and one aft, with each spaced between approximately 1-3 meters apart.

FIG. 5 illustrates an antenna setup for Tx and Rx antennas with an indication of the return length differences between Rx antennas for a CW radar system according to one embodiment of the present invention. The Tx antenna sends out a signal in search of objects in a saltwater environment. Once detected, the signal is first received by the forward Rx antenna, traversing a first return path length (Rx₁). As the CW radar system passes over the detected object, the signal is received by the aft Rx antenna, traversing a second return path length (Rx₂). Because the system is a CW transmission and the return path lengths of the two Rx antennas are different, there is a phase difference between the signals received by the respective Rx antennas. The phase shift is used to distinguish an object and/or target from background noise and approximate the distance between the at least one Tx antenna and the at least one Rx antenna and the object(s) and/or target(s).

In one embodiment, the CW radar system's configuration enables the use of two separate transmitters. In order to accommodate this, the frequency range between the two transmitters needs to be large enough so that the cutoff frequencies block the two transmitters from saturating the other's receivers. Because the two transmitters are perpendicular, the receivers from one transmitter are parallel to the other transmitter and only the frequency cutoff of the antennas will block the opposing transmitter's signal.

FIG. 6 illustrates a phase shift between Rx antennas for a CW radar system according to one embodiment of the present invention. The CW radar system of the present invention looks for the blue channel (Rx₁) to lead to the red channel (Rx₂) in either an increase in signal strength (constructive) or a decrease in signal strength (destructive) as the system gets closer to an object and/or target. However, it is possible for some signals to simultaneously experience constructive interference on one Rx antenna and destructive interference on the other Rx antenna. When detecting multiple targets at various ranges, it is possible for some signals to be constructive and others to be destructive due to distance and orientation from the system. In order to compare the blue channel (Rx₁) to the red channel (Rx₂), the CW radar system normalizes the signals using data recorded in the previous few minutes and subtracts this signal data from the current signal. The previous few minutes of data serves as a baseline for the CW radar system. As more data is collected, the baseline is adjusted. This dynamic baseline adjustment accounts for all sources of signal noise and variation and ensures that all signals from the CW radar system are normalized, improving system accuracy and efficiency. If no targets were present, both channels would indicate signal readings of zero after normalization. Due to fluctuations in electronics and other equipment, the CW radar system is operable to detect approximately −70 to approximately −110 decibel watts (dBW) of signal from the combined noise inputs. This equates to an overall detection sensitivity of approximately 1/1×10¹¹ Watt of signal. In one embodiment, the signal received by the CW radar system in the presence of an object and/or target is at least 45 dBW above the combined noise floor after post processing.

The phase (φ) difference between the multiple Rx antennas is a composite relationship between the direct path signal, the condition of the ocean surface, the vibration in the system's structure, variations occurring at the tow line, and the object and/or target being detected. The magnitude of the signal is proportional to the phase difference between the two signals such that a larger phase difference results in a stronger signal. Therefore, in effect the phase and magnitude of the time difference signal are the same measurement, where one is easier to identify at various times. In one embodiment, the system uses the change in phase signal to detect an object and/or target.

The wavelength in the Rx antenna(s) is equal to the wavelength in the Tx antenna, only with a phase shift based on the distance from the Tx antenna, the object/target, and the Rx antenna(s). In one embodiment of the present invention, when this distance is between approximately 59.7 meters (m) and approximately 119.4 m, the signals create a destructive interference, decreasing the total signal strength below the direct path.

The wavelength (1/frequency) in the Rx antennas is equal to wavelength in the Tx antenna(s), but the signals are phase-shifted based on the distance from the Tx antenna(s) to the object and/or target and back to the Rx antennas. Thus, the phase shift is associated with the difference in distance that the two Rx antennas are perceiving.

For example, if the CW radar system is transmitting at approximately 283 Hz, the perceived wavelength is equivalent to approximately 59.7 m assuming water salinity of approximately 4.95 Siemens, as opposed to approximately 1,000,000 m if transmitted in open air. The path length is a measurement from Tx antenna-to-object/target-to-Rx antennas. In this embodiment, the path length is equal to two-thirds of the wavelength, or approximately 38.6 m, and produces constructive interference in any signal returning from the object/target to the Rx antennas. The result is a direct signal strength of approximately 3.5 dBW from the Tx antenna to either Rx antenna, after amplification from the CW radar system of the present invention. The return signal from an object and/or target that is less than approximately 10 m away will cause the signal in the Rx antennas to increase by more than approximately 1 dBW due to constructive interference. Destructive interference will have the opposite effect and cause the signal to be lower in signal strength.

The CW radar system of the present invention detects a plurality of phase shift samples from a plurality of samples. In one embodiment, the CW radar system is operable to detect between approximately 5-10 samples of phase shift for every 256,000 samples recorded. Additionally, multiple effects are detected in the current system in addition to phase shift between antennas. These include, but are not limited to, differences in signal strength between the Rx antennas and variations in frequency of the signals at each Rx antenna. Although the Tx antenna is producing a constant tone/frequency, there are Doppler effects that occur due to vibrations in the physical structure of the system that result in signal differences between each Rx antenna.

FIG. 7A illustrates variances in signal strength between Rx₁ and Rx₂ antennas for the Rx₁ antenna according to one embodiment of the present invention.

FIG. 7B illustrates variances in signal strength between Rx₁ and Rx₂ antennas for the Rx₂ antenna according to one embodiment of the present invention.

FIG. 7C illustrates variances in frequency using a lower frequency according to on embodiment of the present invention.

FIG. 7D illustrates variances in frequency using a Tx frequency according to one embodiment of the present invention.

FIG. 7E illustrates variances in frequency when using a higher frequency according to one embodiment of the present invention.

Location and Classification

In one embodiment, the CW radar system of the present invention is active sensor-based using electrical conductivity. With an active sensor, signal strength, frequency, and direction can be increased and/or controlled based on the Tx's inputs, polarization, and physical characteristics. An active sensor system increases its operating range by controlling both Tx and Rx characteristics. Ferrous material, including, but not limited to, iron and steel, and non-ferrous material, including, but not limited to, gold, silver, copper, and/or aluminum, are actively excited by the Tx and the EM waves. This creates an electrical current due to the material's conductivity. The physical shape of an object and/or target will produce a return EM wave that is detected by the CW radar system's Rx antennas. The characteristics of the return EM wave are a result of the relationship between the Tx antennas and signals, the Rx antennas and signals, and all conductive material composing and surrounding the total system. Material, such as sand, soil, and/or rock, has such low conductivity that they appear transparent to the Rx antennas, while all conductive materials will produce some level of detection in the Rx antennas.

TABLE 1 Conductivity of Non-Ferrous & Ferrous Metals Material Conductivity (S/m) Sliver  6.3E+07 Copper (annealed) 5.80E+07 Gold 4.11E+07 Aluminum 3.77E+07 Brass (66% Cu, 34% Zn) Copper (annealed) 2.56E+07 Carbon Tungsten 1.79E+07 Zinc 1.67E+07 Cobalt 1.60E+07 Nickel 1.43E+07 Iron 1.03E+07 Platinum 9.52E+06 Tin 9.17E+06 Lead 4.57E+06 Titanium 2.38E+06 Stainless Steel 1.45E+06 Mercury (liquid) 1.04E+06 Bismuth 8.70E+05 Carbon 2.00E+05 Distilled Water 1.00E−04 Dry sandy soil 1.00E−03 Fresh water 1.00E−02 PET 1.00E−21

In one embodiment, the CW radar system transmits a signal from the Tx antenna(s) by creating a specific frequency through the use of a signal generator. In one embodiment, the signal generator functionality includes, but is not limited to, dual channel output, a sampling rate of approximately 150 MegaSamples per second (MSa/s), generation of lower-jitter Pulse waveforms, support for analog and digital modulation types, sweep and burst functions, a harmonics generator function, a high precision frequency counter, standard interface compatibility (e.g., universal serial bus (USB) Host, USB device, local area network (LAN), etc.), a display, channel duplication functionality, and/or remote control operability. In one embodiment, the CW radar system uses a SIGLENT SDG-1025 signal generator. In one embodiment, the CW radar system uses a RIGOL DG-1022 signal generator. In another embodiment, the CW radar system uses a SIGLENT SDG-1032X signal generator. In another embodiment, the CW radar system uses a waveform signal generator.

In one embodiment, the CW radar system transmits a signal from the Tx antenna(s) by using a transmitter computer to create a digital, differential sinewave signal, which is operable to be sent to a digitizer board. A low voltage (+/−1V) sinewave is produced and is then used as an input into a sound stereo amplifier. In one embodiment, the sound stereo amplifier is operable to amplify the low voltage signal, thereby producing an output signal with power between approximately 3500 watts (W) and approximately 5000 W, and is further operable to produce an output signal with amplitude between approximately +/−20 V and approximately +/−600 V. The voltage (power output) limitations of the Tx signals is restricted by the properties of the wires within the Tx antennas. In one embodiment, the Tx antenna uses larger gauge wires and is operable to produce voltages in excess of 600V. In another embodiment, the Tx antenna produces signals between approximately 5-20V.

The output from the transmitter computer is a differential output (i.e., two signals) that are 180 degrees out of phase from one another. Together, these two signals make up a sinusoidal wave.

The returning signal from the Rx antenna(s) is also a differential signal. The return signal is sent from the CW radar system's sensor head up through a data cable to a dinghy. The dinghy contains a global positioning system (GPS) that sends a GPS position through the data cable, along with all the differential signals from each Rx antenna, back to a towing vessel. The incoming signals to the towing vessel are received by at least one impedance matching board that matches the Rx antenna impedance to that of the amplifier boards, which then pass the signal to the receiving computer's digitizer board after amplification. In one embodiment, the impedance is fine-tuned for the CW radar system setup instead of having a set resistor value. In one embodiment, the impedance matching does not drift and does not to be readjusted once it is matched. The incoming analog signal from the Rx antenna(s) is digitized in order to be used by the CW radar system's source code. In one embodiment, the GPS device used on the dinghy and the towing vessel are differential GPS devices.

FIG. 8 illustrates object detection ranges for a CW radar system according to one embodiment of the present invention. The dot at the center represents the CW radar system. A combination of constructive and/or destructive alternating bands indicate which zone the object/target is located in based on the object/target's distance from the Tx/Rx antenna system. In one embodiment, the signal received by the outer channel (Rx₁ channel) is used to analyze the signal received by the inner channel (Rx₂ channel) to determine an upward rise in signal strength (constructive) and/or a downward drop in signal strength (destructive) as the CW radar system is towed/pulled over the object/target. In order to compare the Rx₁ and Rx₂ channels, the signals are normalized using a previously selected time interval of data collected in the absence of an object/target, which is then subtracted from the current signal data. If no objects/targets were located or present, both channels would equate to zero.

In one embodiment, the CW radar system of the present invention uses three principal time domain signals in order to locate objects/targets: signals in the forward Rx antenna, signals in the aft Rx antenna, and the signal difference between the forward and aft Rx antennas. These three signals are then analyzed with respect to energy, power, standard deviation, and phase. All signals are coming from the variation of signals in the time domain.

By using multiple frequencies, the CW radar system of the present invention is able to not only detect and locate objects and/or targets, but classify them as well. This is performed using the relative signal strength and phase between signals of different frequencies, enabling the CW radar system to distinguish between materials including, but not limited to, all ferrous and non-ferrous metals (i.e. gold and/or silver objects). Signals of any frequency can be used to detect all metal objects, but the spectral response or relationship between the frequencies determines the type of metal the object is made of. If an object(s) is made from multiple metal types, the return signal of the CW radar system is a pattern that indicates the individual metals associated with an object and/or target. Because different metals have different conductivities, they will reflect each frequency differently. The signal response from an object and/or target also depends on if the object and/or target is located in a constructive or destructive interference zone. The location and width of the constructive and destructive zone is different for each frequency. Therefore, the CW radar system is operable to detect and classify objects and/or targets using the spectroscopy response of objects and/or targets using multiple frequencies.

FIG. 9 illustrates a precision detector for a CW radar system according to one embodiment of the present invention. The CW radar system is capable of using a single Tx antenna and a single Rx antenna to precisely locate objects and/or targets. The single Tx antenna and the single Rx antenna are connected to one another via a non-conducting pipe/rigid structure. When the CW radar system is stationary, this antenna setup is operable to locate and detect objects and/or targets. In a stationary state, power and frequency will vary across the CW radar system while data is being collected. Moreover, by using a single Tx antenna and a single Rx antenna when the CW radar system is stationary, the CW radar system is operable to pinpoint an object and/or target and determine the object's and/or target's precise depth. In one embodiment, the single Tx antenna and single Rx antenna are the same antennas already incorporated within the CW radar system. In another embodiment, the single Tx and single Rx antenna setup is a separate, detachable antenna setup from the main body of the CW radar system.

The constructive and destructive zones for the CW radar system of the present invention are determined using the distance from the CW radar system to an object/and or target and the return path of the Tx signal to the Rx antennas. This distance represents the total distance associated with a signal from its transmission from the Tx antenna, to its reception by the Rx antenna(s). This distance accounts for frequencies in use by the CW radar system as well.

FIG. 10 illustrates a graph indicating constructive and destructive signals associated with locating an object in a saltwater environment according to one embodiment of the present invention. When an object and/or target is detected by the CW radar system in a constructive zone, an increase in signal strength is detected as the CW radar system approaches the object and/or target, and a decrease in signal strength is detected as the CW radar system moves away from the object and/or target. When an object and/or target is detected by the CW radar system in a destructive zone, a decrease in signal strength is detected as the CW radar system approaches the object and/or target, and an increase in signal strength is detected as the CW radar system moves away from the object and/or target. In one embodiment, this appears on a graph as a double-hump shape, indicating that all Rx antennas detected the object and/or target.

FIG. 11A illustrates a graph indicating constructive and destructive zones over time created by the signals collected using the sensor head, a tow vessel, and a dinghy associated with locating an object in a saltwater environment according to one embodiment of the present invention. The movement of the sensor head associated with a towing by the vessel system determines when and where signals are transmitted and received by the corresponding Tx and Rx antennas. In addition, the CW radar system must monitor its output energy product.

FIG. 11B illustrates a graph indicating the energy product for a CW radar system according to one embodiment of the present invention.

FIG. 11C illustrates a graph indicating antenna signal strength associated with constructive and destructive zones of a CW radar system according to one embodiment of the present invention.

FIG. 11D illustrates a graph indicating a fore and aft antenna energy product associated with constructive and destructive zones of a CW radar system according to one embodiment of the present invention.

In one embodiment, a towing vessel attaches a tow line and/or tow cable to a dinghy, wherein the dinghy is attached, via a second tow line and/or tow cable, to the sensor head of the CW radar system of the present invention. In one embodiment, the CW radar system includes a tow line and/or tow cable for connecting the towing vessel to the dinghy and a tow line and/or tow cable for connecting the dinghy to the CW radar system as well as a data tow line and/or data tow cable connecting the towing vessel to the dinghy and a data tow line and/or data tow cable connecting the dinghy to the CW radar system. In one embodiment, the dinghy includes a global positioning system (GPS) receiver. Because the CW radar system is located underwater, the GPS receiver must be placed on the attached dinghy and not the CW radar system. An initial calibration of the CW radar system components is performed and a baseline for object and/or target geolocation data is established. In one embodiment, the baseline signal for a constructive zone is louder and the signal is elevated. In one embodiment, the negative energy in a destructive zone is quieter. The towing vessel travels in a line over a target survey area at an optimum speed. The CW radar system is operable at speeds between approximately 0 to >30 kts. In one embodiment, the optimum speed of the towing vessel is between approximately 3 kts to 8 kts to reduce vibrational noise interference. Once the towing vessel, the dinghy, and the CW radar system have traveled over the target survey area, the towing vessel turns approximately 90° and specifies a new line of travel over the target survey area. In one embodiment, the towing vessel turns clockwise. In another embodiment, the towing vessel turns counterclockwise. This new line is covered by the towing vessel, the dinghy, and the CW radar system. In one embodiment, the CW radar system is operable to send and receive signals within a range of approximately 30-100m from each side of the CW radar system when traveling in a line, resulting in a total swath width of approximately 60-200m in one pass. In another embodiment, the CW radar system is operable to send and receive signals within a range of 200m from either side of the CW radar system when traveling in a line, resulting in a total swath width of 400 m per pass. In one embodiment, the lines of travel taken by the towing vessel, the dinghy, and the CW radar system over the target survey area are approximately 100m apart from each other.

In one embodiment, the towing vessel, the dinghy, and the CW radar system traverse the same part of the target survey area multiple times in order to more accurately identify the size, structure, shape, and composition of the object and/or target. This process is repeated in a set pattern until the target survey area has been completely mapped by the towing vessel, the dinghy, and/or the CW radar system. By travelling over the target survey area in a designated pattern using the towing vessel, the dinghy, and the CW radar system, the CW radar system collects data that can be associated with the geolocation of underwater ferrous and/or non-ferrous objects. This is because when the CW radar system travels over an object and/or target, a change in signal strength is detected followed by a change in signal strength in the opposite direction as the towing vessel, the dinghy, and the CW radar system moves away from a detected object and/or target. When the data has been processed, the CW radar system returns Gaussian-like curves in the area where an object and/or target has been located, indicating detection from the front and rear antennas of the CW radar system. In one embodiment, the CW radar system returns lines and/or scatter trails indicating an object and/or target. The CW radar system passes over an area multiple times in order to generate tighter lines around the object and/or target. In one embodiment, the CW radar system is connected directly to the towing vessel via a single tow line, without the use of a connecting dinghy.

In one embodiment, the CW radar system detects changes in signal strength the first time it passes over an object and/or target. The CW radar system then passes over the same area again and varies the power level of the signal in order to collect more data on the object and/or target. A lower power signal provides more detail and higher fidelity images of the object and/or target. In one embodiment, the power level of the signal depends on the pattern used to survey the area. In one embodiment, the CW radar system makes tighter passes over the same part of the target survey area in order to detect more information about an object and/or target in that part of the target survey area. In one embodiment, the pattern that the CW radar system takes over the target area and the power variations in the signal are set before the CW radar system begins traversing the target area in order to capture full detail of the target area. In another embodiment, the pattern that the CW radar system takes over the target area and the power variations in the signal are dependent on the readings of the Rx antenna. When the CW radar system detects changes in signal strength the first time it passes over an object and/or target, it modifies the subsequent path and signal transmission in order to obtain further information about the detected object and/or target. In one embodiment, the power level of the signal used to identify the object and/or target is controlled by the gain of the Rx amplifier board. In another embodiment, the power level of the signal used to identify the object and/or target is controlled by the Tx antennas. In yet another embodiment, the power level of the signal used to identify the object and/or target is controlled by both the Tx and the Rx antennas. In one embodiment, the CW radar system is operable to identify the size, structure, and shape of an object and/or target with multiple radar readings. For example, the CW radar system is operable to identify ribs on a barge and brass shells in an underwater environment.

FIG. 12A illustrates a three-dimensional (3D) underwater depth map indicating areas where no objects and/or targets were detected by a CW radar system according to one embodiment of the present invention. If the CW radar system detects an object and/or target, a spike in signal strength would have been detected as the bow and aft Rx antennas approached and moved away from underwater objects and/or targets. The lack of a significant increase/decrease in signal strength (blue) compared to background noise indicates that no objects and/or targets were detected. The background noise level typically will vary slightly as indicated in the small spikes in the blue peaks. An object and/or target that is closer to the CW radar system will result in a stronger signal reading by the Rx antennas.

FIG. 12B illustrates a 3D underwater depth map indicating multiple detected objects by a CW radar system according to one embodiment of the present invention. The multiple blue-green and yellow colored spikes present on the 3D underwater depth map indicate that both the bow and aft Rx antennas detected an object and/or target (i.e., multiple increases and decreases in signal strength). These spikes occur as the bow and aft Rx antennas approach and move away from underwater objects and/or targets.

FIG. 13A illustrates a 3D underwater depth map indicating the location of objects according to one embodiment of the present invention. Once a survey for a target area is performed using the CW radar system of the present invention, the collected data is operable for display via mapping software. In one embodiment, the collected data indicates information including, but not limited to, an object and/or target depth, a geolocation for an object and/or target, a north value, a west value, an east value, and/or a south value. In one embodiment, the geolocation for an object and/or target is a set of coordinate points.

FIG. 13B lists all of the labels in FIG. 13A representing different geographic locations for detected objects according to one embodiment of the present invention.

FIG. 14A illustrates a two-dimensional (2D) underwater depth map indicating location coordinates for a detected object according to one embodiment of the present invention. This underwater depth map indicates a sampling region for the CW radar system. The 2D underwater depth map is shown from a South-to-North and West-to-East perspective.

FIG. 14B lists all of the labels in FIG. 14A representing different geographic locations for detected objects according to another embodiment of the present invention.

FIG. 15A illustrates a 2D underwater depth map indication location coordinates for detected objects according to another embodiment of the present invention.

FIG. 15B lists all the labels in FIG. 15A representing different geographic locations for detected objects according to one embodiment of the present invention.

FIG. 16A illustrates a surveying operation with a CW radar system according to one embodiment of the present invention. The CW radar system is connected to a towing vessel. As the CW radar system travels over ferrous and/or non-ferrous metal objects, the CW radar system is operable to identify a plurality of buried test sites.

FIG. 16B illustrates a surveying operation with a CW radar system connected to a towing vessel according to one embodiment of the present invention. The CW radar system is connected to the towing vessel via a tow cable and at least one data cable. The tow cable includes a plurality of tow cable floats, wherein the plurality of tow cable floats are operable to prevent the tow cable and the at least one data cable from sinking below the surface of the water when the towing vessel is not moving.

FIG. 17A illustrates a 2D underwater heatmap indicating the geolocation of detected objects according to one embodiment of the present invention. The 2D underwater heatmap further includes an indication of density and/or intensity. In one embodiment, the 2D underwater heatmap is overlayed with magnetometer search tracks. When overlayed with the magnetometer, the CW radar system is able to locate all metal objects and/or targets, while simultaneously eliminating the ferrous objects and/or targets. In one embodiment, the return phase and amplitude differences in each heat map are used to distinguish between specific metal types. In one embodiment, the identification of different metal types is done automatically and in near real-time.

FIG. 17B lists all of the labels in FIG. 17A representing different priority zones on a 2D underwater heatmap for a CW radar system according to one embodiment of the present invention, where priority zones represent areas where at least one or more object(s) and/or target(s) were detected by the CW radar system.

FIG. 18 illustrates a 2D underwater depth map indicating the geolocation of detected objects according to another embodiment of the present invention.

FIG. 19A illustrates a 2D underwater heatmap indicating the geolocation of detected objects according to another embodiment of the present invention. The 2D underwater heatmap includes a plurality of priority zones, indicating analyzed areas with detected objects. In addition, the 2D underwater heatmap further includes a density and/or an intensity for each priority zone.

FIG. 19B lists all of the labels in FIG. 19A representing different priority zones on a 2D underwater heatmap for a CW radar system according to one embodiment of the present invention.

FIG. 20A illustrates a 2D underwater heatmap indicating a CW radar system traveling path and the geolocation of detected objects according to another embodiment of the present invention. The 2D underwater heatmap indicates priority zones detected by the CW radar systems. The 2D underwater heatmap further includes an indication of intensity and/or density for each priority zone and/or detected object and/or target.

FIG. 20B lists all the labels in FIG. 20A representing different geographic locations for detected objects according to one embodiment of the present invention.

FIG. 21A illustrates a 2D graph indicating underwater reef and submerged sandbars (in dark brown) and a travel route for a CW radar system according to one embodiment of the present invention. At the beginning of a surveying operation, a target region is established. With the target region established, a towing vessel begins towing the CW radar system in a line pattern (i.e., the travel route) over the target region. In one embodiment, the towing vessel is connected to the CW radar system via a dinghy. A towing cable and a data cable connect the towing vessel to the dinghy, and the dinghy connects to the CW radar system via a towing cable and/or data cable. In one embodiment, the towing vessel is connected to the CW radar system via a towing cable and/or data cable in addition to a dynamic winch system. The dynamic winch system is operable to facilitate the sensor head depth during towing. In one embodiment, the towing vessel is connected to the CW radar system via a towing cable and/or data cable in addition to the use of a dynamic down plane system on or ahead of the sensor head. The dynamic down plane system is operable to facilitate the sensor head depth during towing.

FIG. 21B illustrates a 2D heatmap graph indicating a travel route for a CW radar system according to one embodiment of the present invention. By repeatedly crossing over a target region, the CW radar system is operable to detect objects and/or targets with greater accuracy. This is possible using the combination of the bow and aft Rx antennas of the CW radar system, providing multiple opportunities for object and/or target detection.

The CW radar system of the present invention includes at least one amplifier board. Current commercially-available amplifier boards are unable to meet the amplification and dynamic range requirements of the present invention. Commercially available amplifier boards typically amplify at specific levels or ranges (e.g., 20-40 dB, 40-60 dB, 60-80 dB, etc.). More specifically, these commercial amplifier boards only enable a user to step through each decibel range at limited levels (i.e., by one-half or full decibels at each one of the available levels). Thus, these commercial amplifier boards are not sensitive enough and/or do not offer enough dynamic and detailed control for the CW radar system of the present invention. While the amplifier board(s) of the CW radar system are digital-to-analog (D-A) and analog-to-digital (A-D) amplifier boards, the CW radar system requires a step size of approximately 1/1,000 decibels (dB), which is not typically available with commercial amplifiers and amplifier boards.

Moreover, commercial amplifier boards experience difficulties when balancing two antennas within close proximity to one another, including, but not limited to, issues balancing the signal-to-noise ratio and/or issues relating to overall power output for a radar system. Traditional amplifier boards cannot reach the decibel ranges required of the CW radar system of the present invention. The CW radar system requires the amplifier board to be able to operate between approximately 60 dB to approximately 150 dB. The CW radar system also requires the amplifier board to compensate for the DC biasing offset voltage without losing system gain. These functions are accomplished through hardware circuitry design and software control logic.

Due to the extremely low frequency (ELF) signals involved, an amplifier board built to handle the specific search frequencies is required, incorporating a direct current (DC) voltage to less than 10 Volts (V). There are no commercially available amplifier boards with both dynamic range and amplification operable to achieve the necessary precision of the CW radar system of the present invention.

FIG. 22A illustrates an amplifier board for a CW radar system according to one embodiment of the present invention. The amplifier board includes, but is not limited to, an output stage and/or an input stage. The amplifier board is operable to handle output voltages between approximately 10 V to more than approximately 600 V through the Tx antenna(s). In one embodiment, the amplifier board of the present invention is a three-stage circuit. The first stage is an n-amp (instrumentation amplifier), that amplifies the differential voltage between input wires. A differential voltage is used to create the signal because the input to the amplifier board comes from a dipole antenna that is not grounded to the amplification board. The first stage is operable to provide up to approximately 80 decibels (dBs) of gain. In one embodiment, the first stage n-amp is operable to provide more than approximately 80 dBs of gain. The second stage is an operational amplifier (op-amp), operable to provide up to approximately 40 dBs of gain. In one embodiment, the second stage op-amp is operable to provide more than approximately 40 dBs of gain. The third stage is a band-pass filter, operable to provide approximately 2 dB of gain. In one embodiment, the third stage band-pass filter is operable to provide more than approximately 2 dB of gain.

FIG. 22B illustrates a pin configuration diagram for an amplifier board for a CW radar system according to one embodiment of the present invention. In one embodiment, the amplifier is an AD622 amplifier board. AD622 amplifiers require only one external resistor to set any gain between approximately 2 dBs and approximately 100 dBs. For a gain of 1 dB, no external resistor is required.

FIG. 22C illustrates a pin connection diagram for an amplifier board for a CW radar system according to one embodiment of the present invention. In one embodiment, the amplifier board is an AD8421 amplifier board. AD8421 amplifier boards operate at a low cost, low power, extremely low noise, ultralow bias current, and include high speed instrumentation suited for signal conditioning and data acquisition applications.

FIG. 22D illustrates a pin configuration and function diagram for an amplifier board for a CW radar system according to another embodiment of the present invention.

FIG. 22E illustrates a pin configuration and function diagram for an amplifier board for a CW radar system according to another embodiment of the present invention.

FIG. 22F illustrates a chart depicting the flow of signal through an amplifier board for a CW radar system according to one embodiment of the present invention. The chart depicts four stages of signal flow throughout the amplifier board. While stage one is always required, the signal flow is operable to flow through any combination of the remaining stages. By eliminating a stage from the signal flow, the overall noise added to the CW radar system is reduced. In one embodiment, the flow of signal through the amplifier board is multi-stage and the amplification values and stages used are all computer controlled. The amplifier board further includes a wiring harness operable to read all amplifier board inputs and settings, and then send the proper setting signals in order to calibrate each board in the system. Each wiring harness includes a plurality of output control cables to Rx antennas and at least one computer input side. In one embodiment, the flow of the signal through the amplifier board depends on the location of the boat and the presence of radiofrequency interference and noise from external sources. When the boat is closer to a land mass, there is increased interference from power grids and other signal sources. In one embodiment, the power grid interference includes a 60 Hz signal. In another embodiment, additional harmonics cause further interference in the system. In one embodiment, the four-stage amplifier board is operable to eliminate the interference via a series of filters. In another embodiment, the signal does not flow through all four stages of the amplifier board. In one embodiment, the stages of amplification are chosen to reduce the amount of overall noise added to the CW radar system.

FIG. 23 lists a table for a primary gain stage of an amplifier board for a CW radar system according to one embodiment of the present invention. The primary gain stage includes resistor combinations and settings for an Rx antenna gain controller.

FIG. 24 lists a table for a secondary gain stage of an amplifier board for a CW radar system according to one embodiment of the present invention. The secondary gain stage includes resistor settings for an Rx antenna gain controller. The various stage settings are measured in units of ohms (Ω). In addition, the stage settings include resistor settings for an Rx antenna gain controller.

FIG. 25 lists a table for Stage One and Stage Two gain settings for an amplifier board for a CW radar system according to one embodiment of the present invention. The various stage settings are measured in units of kiloohms (kΩ). In addition, the stage settings include resistor settings for an Rx antenna gain controller.

The amount of gain provided by the three-stage circuit setup is individually determined for each Rx antenna. While the antennas used, both Tx and Rx, are interchangeable, they each have their own capacitance and performance curves. In addition, corresponding logic-controlled circuitry enables capacitance matching between the transmitter, amplifier, and antenna(s). This requires that each antenna have its own amplification settings, or gain, when used as a Rx antenna. In addition to this gain, the system of the present invention uses oversampling to provide another gain due to processing gain. In one embodiment, the oversampling is operable to provide approximately 24 dBs of gain. In one embodiment, the CW radar system is operable to sample at approximately 256,000 times a second. In addition, the amplifier board includes both low and high frequency pass filters, with gain controls from less than approximately 2 dB to more than approximately 130 dB.

FIG. 26 lists a table for gain calculations for an amplifier board for a CW radar system according to one embodiment of the present invention. The stage settings are measured in units of ohms (Ω). In addition, the stage settings include resistor settings for an Rx antenna gain controller.

FIG. 27 lists a table for Stage One and Stage Two gain settings for an amplifier board for a CW radar system according to another embodiment of the present invention.

FIG. 28A lists a table for resistance values for an amplifier board for a CW radar system according to one embodiment of the present invention.

FIG. 28B lists a table for additional resistance values for an amplifier board for a CW radar system according to one embodiment of the present invention.

FIG. 28C lists a table for additional resistance values for an amplifier board for a CW radar system according to one embodiment of the present invention.

In one embodiment, the amplifier board(s) of the CW radar system of the present invention operate in four stages. The first stage requires the CW radar system to turn multiple signals into a single signal, used for object and/or target geolocation. Next, a low-pass anti-aliasing filter is applied to the single signal. This low-pass filter removes unnecessary frequencies from the system. The third and fourth stages are identical, and involve the removal of noise associated with any direct current (DC) offset in order to isolate the signal. Each stage introduces between approximately 1.5 dBs to approximately 271 dBs gain per stage. Once the signal is isolated, the various Tx and Rx antennas are balanced, resulting in an output indicating the geolocation of an object and/or target. In one embodiment, the amplifier board is digitally controlled. In one embodiment, the amplifier board is automatically controlled. In another embodiment, the amplifier enables a user to select the cutoff frequency from a range of approximately 106 Hz to approximately 3,000 Hz. For low-band frequencies, the cutoff frequency is between approximately 106 Hz and approximately 280 Hz. For mid-band frequencies, the cutoff frequency is between approximately 220 Hz and approximately 650 Hz. For high-band frequencies, the cutoff frequency is between approximately 500 Hz and approximately 3,000 Hz.

The raw signals received by the Rx antennas are on the order of a pico-volt or less. These ultra-faint signals are amplified by between approximately 70 dB and approximately 120 dB of gain, with a maximum board gain capability of more than approximately 155 dB. In one embodiment, the typical gain of the system is between approximately 100-110 dB in order to avoid saturation. In one embodiment, the amplification of the at least one amplifier board optimizes the signal-to-noise ratio (SNR) to minimize noise from vibrations and other sources. In one embodiment, the at least one amplifier board is contained in a two-step noise reduction system. First, impedance matching and receiver amplifier boards are housed inside shielded and grounded metal boxes functioning as a Faraday cage, preventing electromagnetic interference (EMI). Second, each box is housed inside a thermo-electric cooler and/or heater in order to maintain a near constant operating temperature. This prevents thermal noise from entering the amplifier boards in any environmental condition.

All connectors entering the EMI boxes are shielded and grounded. In addition, any openings present on the EMI boxes are covered with an aluminum mesh, wherein the mesh is also grounded to the EMI box. In another embodiment, the mesh is a copper mesh. At the frequencies used by the CW radar system, the aluminum mesh visually appears “open,” but in reality, is an electrical barrier to all frequencies below approximately 10,000 Hz. Without EMI shielding, the amplification process is reduced by approximately 30-60 dB which is insufficient for the signals coming from the Rx antennas. In one embodiment, each Rx antenna in the CW radar system has its own EMI box. Each EMI box is then placed inside a refrigerated container for climate control. In one embodiment, the frequencies used by the CW radar system are approximately 3,000 Hz or less.

Amplification occurs in two stages. The first stage involves direct current (DC) removal and isolation. The DC removal and isolation techniques are described in Kresimir Odorcic (2008). “Zero DC offset active RC filter designs,” ThinklR: The University of Louisville's Institutional Repository, which is incorporated herein by reference in its entirety. Stage two represents the digitally-controlled amplification stage. By using digital relays in conjunction with fixed resistors in series-parallel networks, the CW radar system is able to digitally change amplification values. These stages include approximately 1,000,000 linear gain steps that are capable of amplification from approximately 35 dBs to approximately 156 dB s.

The amplifier boards used in the present invention account for all amplification processes, DC offset issues, and/or low-pass filtering requirements.

The CW radar system requires the use of a digitizer, a hardware device that receives analog information, including light and/or sound, and records it digitally. This process is known as digitization. The digitizer board includes a connector box, an input device for receiving input from a transmitter computing device, and/or an output device for sending output to a receiver computer device.

Digitizer boards used in the present invention are operable to take between approximately +10 volts (V) and approximately −10V. During operation of the CW radar system, power levels fluctuate due to clutter and noise issues. By operating between approximately +10V and approximately −10V, the CW radar system is able to avoid saturation that occurs at voltages greater than approximately +10V and less than approximately −10V. In addition, operating between the range of approximately +10V and approximately −10V requires approximately 3.5 decibel watt (dBW) in power. When a detection and/or collection operation begins, the Rx antenna(s) start with a signal measuring approximately 50 nanovolts (nV) with no object and/or target detected.

All of the hardware components of the CW radar system of the present invention are subject to constant temperature regulation as well. While no specific temperature is required, the system must operate at a single, constant and/or near-constant temperature. In one embodiment, the temperature of the CW radar system is maintained using a thermally-controlled refrigerator, containing the EMI-shielded amplifier boxes. The CW radar system temperature is maintained using cooling and/or heating. The refrigerator(s) holding the EMI-shielded amplifier boxes are operable to cool and/or heat the air around the amplifier boxes in order to reduce the amount of thermal drift in the impedance matching and amplifier electronics. By maintaining the temperature of the CW radar system at a constant and/or near-constant temperature, the system avoids experiencing large temperature swings which are operable to decrease system accuracy, efficiency, and/or operability.

In addition to temperature issues, the CW radar system of the present invention also accounts for alternating current (AC) power issues. Because the CW radar system is towed, in a saltwater environment, from a vessel, the vessel presents a grounding problem to the system. On land, grounding issues are simple: AC wiring systems including a green grounding wire, preventing shocks and electrocution. The ground connection is completed by clamping the AC wiring system to a metal water pipe or by driving a long copper stake into the ground. However, water-based vessels are not grounded the same. Many water-based vessels make use of a plate enabling the vessel to ground itself to the ocean. Grounding for water-based vessels represents an additional source of noise that the CW radar system of the present invention must account for.

Post Processing

Post processing software is used in conjunction with the CW radar system of the present invention. Post processing software functionality includes, but is not limited to, eliminating variances in boat speed, eliminating GPS timing differences across all GPS receivers used during collection, eliminating variances in computer timing across all computers used during collection, eliminating variances associated with the depth of the CW radar system, real-time or near real-time object and/or target detection, survey automation, adjusting controls related to a towing vehicle's navigational capabilities, object and/or target classification, and/or automated object and/or target identification. Object and/or target classification includes, but is not limited to, size, location, and a potential material type. In one embodiment, the post processing software used is MATLAB (available from MATHWORKS). In one embodiment, the post processing software used is PYTHON. In one embodiment, the post processing software used is C/C++. In one embodiment, the post processing software used is JAVA. In one embodiment, the post processing software is operable to detect objects and/or targets and their compositions in real time. In another embodiment, the post processing software is operable to detect objects and/or targets and their compositions in near real time.

Post processing must also account for a direct current (DC) offset. DC offset occurs when hardware components add DC voltage to audio signals. For example, an amplifier board of the present invention emits an additional DC microvolt into the signals received by the Rx antenna(s). Due to the sensitivity of the system, this additional microvolt represents a major positive or negative shift in signal reception. This shift leads to a saturation in signal reception.

In addition, the CW radar system makes use of a multi-step process for specifically identifying objects and/or targets of interest, as well as the material each object and/or target is made of. In one embodiment, the multi-step process includes, but is not limited to, raw data collection, frequency offset, frame stitching, narrow band filtering, and/or elimination of discontinuities.

Raw data collection refers to the continuous stream of data coming from the Rx antenna amplifier boards, as well as corresponding GPS location data using a towing vessel and a dinghy. In one embodiment, every ⅕^(th) second of data from the Rx antenna amplifier boards and the corresponding GPS location data are recorded. This raw data collection is performed using the above-mentioned digitizer boards. In one embodiment, the digitizer boards are operable to digitize the raw data at a rate of approximately one million bits per second. The CW radar system further oversamples the raw data in order to increase the overall signal-to-noise ratio. In one embodiment, oversampling at a rate of approximately 250,000 samples per channel yields an increase in gain for the system between approximately 18 dB and approximately 26 dB.

As the CW radar system of the present invention detects both amplitudes and phase returns from objects and/or targets on or under the ocean floor, the frequency offset must be constantly monitored and corrected for. Any transmit frequency will vary slightly with time and environmental changes due to the electronic equipment used. Therefore, the frequency offsets in the return signal in the Rx antennas must be continually adjusted. A constant frequency offset function is applied to the raw data as it is collected by the CW radar system in order to balance out the transmit frequency variations.

The frame stitching process involves stitching the individual data files collected by the CW radar system into an array, covering hours of data collection. This frame stitching process additionally solves for GPS and timing discontinuities. If a single micro-second of data is lost, this results in a discontinuity in the phase shifting, causing false signals to be inserted into the collected data. In order to solve this problem, in one embodiment the CW radar system uses at least one GPS receiver in order to reduce the loss of GPS data when closing one second of array data and starting a new second of array data.

Once the raw data has been stitched together, a narrow band tap filter is applied to the continuous signal in order to eliminate the vibration and motion of the sensor head through the water. The narrow band tap filter is adjustable depending upon the environmental conditions including, but not limited to, sea-state, towing speed, depth, and/or a tow distance of the CW radar system behind a towing vessel and/or dinghy.

The last post-processing step eliminates any discontinuity associated with last data in the large, multi-hour array of signal data. Once discontinuities are eliminated, the CW radar system creates a filtered data set. Using this filtered data set, any aliasing effects are eliminated by taking a moving sixty-second window of data and further processing the center thirty seconds of data in the sixty-second window. The edges of the sixty-second data file are where the aliasing effects manifest, meaning the center thirty-seconds of data are free of these effects. In addition, the filtered data set is used to correct the phase offset between the bow Rx antenna(s) of a specific band when compared against the aft Rx antenna(s) of the same specific band.

Once the filtered data set has been phase offset corrected, the compiled data array is used to analyze the surveyed area. Any statistical data is also stored along with the compiled array, which are both then used in conjunction with the sensor head's GPS position with respect to the surveyed area. In order to simplify the post-processing functions, areas before, during, and after a turn in a surveyed area are marked and set aside. This is because during a turn, the path of the CW radar system through the water varies not only in direction, but also in speed, depth, and physical orientation relative to the surface of the water. This variance in shallow depth surveys (i.e., surveys in a body of water with a depth less than 100 ft.) causes a rotation of the CW radar system when being towed from a towing vessel, such that the surface reflections from the ocean and any wave action cause excessive noise and/or false targeting within the collected data.

In one embodiment, the software of the CW radar system includes at least one graphical user interface (GUI). The at least one GUI is operable to display information including, but not limited to, Tx antenna health, Rx antenna health, object and/or target geolocation, a geolocation for the CW radar system, a geolocation for a dinghy, a system temperature indicator, a vessel status indicator, a speed indicator, an environmental temperature indicator, an object/and or target depth indicator, an object and/or target material, an object and/or target size, a Tx antenna signal status, and/or a Rx antenna signal status.

This functionality is achieved using a combination of the CW radar system's amplifier board and impedance matching boards. Impedance matching refers to designing input impedance of an electrical load and/or the output impedance of its corresponding signal source in order to maximize the power transfer and/or minimize signal reflection from the electrical load. The electrical and antenna components of the present invention have a corresponding impedance (i.e., impedance going out from the amplifier output signal). When transmitting a specific signal, the CW radar system of the present invention verifies that the impedance associated with the electrical equipment sending the specific signal matches the impedance of the Tx antenna sending out the signal. In addition, the return signal from the Rx antenna(s) must also match its impedance.

FIG. 29A illustrates the top of an impedance matching board for a CW radar system according to one embodiment of the present invention.

FIG. 29B illustrates the bottom of an impedance matching board for a CW radar system according to one embodiment of the present invention.

The Tx antennas require their own specialized impedance matching board. The input to this impedance matching board comes from a sound system amplifier and the output goes directly to the Tx antennas via a data cable.

In one embodiment, the amplifier and impedance matching boards are all computer controlled. This enables the system to automatically and/or autonomously balance all of the values present in order to maximize the signal going out to the Tx antennas and the signal coming back from the Rx antennas.

As previously mentioned, the CW radar system of the present invention includes a multiplicity of graphical user interfaces (GUIs), with GUIs including, but not limited to, three-dimensional (3D) maps for an underwater environment, sonar transmission and receiving, object and/or target detection mapping, receiver controls, transmission controls, and/or two-dimensional (2D) maps for an underwater environment.

FIG. 30 illustrates a graphical user interface (GUI) for displaying objects detected by a CW radar system according to one embodiment of the present invention. The GUI is operable to provide a three-dimensional (3D) map of a saltwater environment, indicating the presence of any detected objects and/or targets. The 3D map of the saltwater environment is able to be viewed from a West-to-East and South-to-North perspective. When objects are detected, the GUI displays a double-hump-like 3D image. This occurs because an object is first detected by the bow Rx antennas of the CW radar system, creating a rise in signal strength. This detected signal strength drops as the bow of the CW radar system passes over the detected object. Then, as the aft Rx antennas of the CW radar system detect the object, a second rise in signal strength is detected. As the aft of the CW radar system moves away from the detected object, a drop in signal strength occurs. The combination of the bow and aft Rx antenna detections results in a double-hump-shape on the GUI, indicating that an object has been detected. In one embodiment, the CW radar system is operable to detect and identify objects and/or targets in real time or near-real time. The movement of the CW radar system generates 2D and 3D images of the target survey area with a multiplicity of lines.

FIG. 31 illustrates a GUI for displaying objects detected by a CW radar system according to another embodiment of the present invention. The GUI displaying the 3D map of the saltwater environment is able to be viewed from a South-to-North and West-to-East perspective.

FIG. 32 illustrates a sonar GUI for a CW radar system according to one embodiment of the present invention. The sonar GUI is operable to display elements including, but not limited to, a start recording time, an end recording time, a heading, a range, a distance, a measurement of the distance divided by a sonar ping, an altitude, a travel route, an inline stretch value, a range limit, a view selection drop-down box, a channel selection, a color scheme selection, an auto refresh option, a compass, a list of detected objects and/or targets, and/or a tile identification (ID) number.

FIG. 33 illustrates a travel route GUI for a CW radar system according to one embodiment of the present invention. The travel route GUI is operable to display information including, but not limited to, a travel route for the CW radar system, an object and/or target detection indication, and/or a depth value. The travel route for the CW radar system is displayed as a green line, indicating the positions the CW radar system has traveled over. As the CW radar system continuously travels over a target region, objects and/or targets are detected by the Rx antennas at the bow and aft of the CW radar system. The stronger the received signal by the Rx antennas, the darker the indication on the map (i.e., the red dots on the map). A cluster of red dots is also an indication of a detected object and/or target, as this indicates a strong signal detected by the bow and aft Rx antennas. In one embodiment, the travel route GUI is displayed using color images. In one embodiment, the travel route GUI is displayed in black and white images.

FIG. 34A illustrates a two-dimensional (2D) map indicating a log scale of a normalized energy product for a CW radar system with no detected targets according to one embodiment of the present invention. The lack of detected objects is indicated by the absence of connecting lines between target points. As the CW radar system travels over a region, objects are first detected by the bow Rx antennas and then detected a second time by the aft Rx antennas. This detection pattern is visualized by solid lines, indicating that an object and/or target was detected by both sets of Rx antennas as the CW radar system passed over the object and/or target.

FIG. 34B illustrates a 2D map indicating a log scale of a normalized energy product for a CW radar system with detected targets according to another embodiment of the present invention. Detected objects are indicated by the presence of connecting red lines between target zones. These red lines indicate that both the bow and aft Rx antennas received a corresponding return signal from an object and/or target. This occurs as the bow Rx antennas cross over a detected object and/or target and then move away from the detected object and/or target, with the aft Rx antennas then detecting the object and/or target followed by an increase in distance from the object and/or target. Thus, an object is detected by the CW radar system twice, once as the bow Rx antennas are towed over the object and a second time as the aft Rx antennas are towed over the object. This results in increased accuracy relating to object and/or target detection of both ferrous and non-ferrous metals in saltwater environments.

FIG. 35A illustrates a 2D density and intensity map for a CW radar system according to one embodiment of the present invention.

FIG. 35B illustrates a 2D density map for a CW radar system according to one embodiment of the present invention.

FIG. 36 illustrates a GUI for displaying energy and frequency data associated with a CW radar system according to one embodiment of the present invention. The GUI is operable to display information including, but not limited to, a graph indicating an energy of difference of time domain signals, a graph indicating a product of energy, a graph indicating a standard deviation from antennas and power density, a graph indicating a difference in power history, a survey track map, a boat speed and/or direction, a time, a channel 1 frequency, a channel 1 power value, a channel 2 frequency, a channel 2 power value, a mean, a standard deviation, a frequency offset value, a set of average phase values, a peak frequency distance, and/or a normalized energy product value. The red and blue lines correspond to the signal return from two Rx antennas. The green line is the power density spectrum calculation, which is derived from the signal return of the Rx antennas. The GUI is further operable to display a survey track in the lower right corner of the GUI. In another embodiment, the GUI has a set(s) of user-defined windows to monitor, track, and display various component(s), system(s), and external values.

FIG. 37 illustrates a GUI for displaying phase detail and power history data associated with a CW radar system according to one embodiment of the present invention. The GUI is operable to display information including, but not limited to, a graph indicating subsecond phase detail, a graph indicating subsecond power history for both a bow and aft normalized energy product, and/or a graph indicating a subsecond difference power history using a mean and standard deviation. The blue and red lines correspond to a signal return from two Rx antennas. The green line is a power density spectrum calculation derived from the signal return from the two Rx antennas.

FIG. 38 is a schematic diagram of an embodiment of the invention illustrating a computer system, generally described as 800, having a network 810, a plurality of computing devices 820, 830, 840, a server 850, and a database 870.

The server 850 is constructed, configured, and coupled to enable communication over a network 810 with a plurality of computing devices 820, 830, 840. The server 850 includes a processing unit 851 with an operating system 852. The operating system 852 enables the server 850 to communicate through network 810 with the remote, distributed user devices. Database 870 is operable to house an operating system 872, memory 874, and programs 876.

In one embodiment of the invention, the system 800 includes a network 810 for distributed communication via a wireless communication antenna 812 and processing by at least one mobile communication computing device 830. Alternatively, wireless and wired communication and connectivity between devices and components described herein include wireless network communication such as WI-FI, WORLDWIDE INTEROPERABILITY FOR MICROWAVE ACCESS (WIMAX), Radio Frequency (RF) communication including RF identification (RFID), NEAR FIELD COMMUNICATION (NFC), BLUETOOTH including BLUETOOTH LOW ENERGY (BLE), ZIGBEE, Infrared (IR) communication, cellular communication, satellite communication, Universal Serial Bus (USB), Ethernet communications, communication via fiber-optic cables, coaxial cables, twisted pair cables, and/or any other type of wireless or wired communication. In another embodiment of the invention, the system 800 is a virtualized computing system capable of executing any or all aspects of software and/or application components presented herein on the computing devices 820, 830, 840. In certain aspects, the computer system 800 is operable to be implemented using hardware or a combination of software and hardware, either in a dedicated computing device, or integrated into another entity, or distributed across multiple entities or computing devices.

By way of example, and not limitation, the computing devices 820, 830, 840 are intended to represent various forms of electronic devices including at least a processor and a memory, such as a server, blade server, mainframe, mobile phone, personal digital assistant (PDA), smartphone, desktop computer, netbook computer, tablet computer, workstation, laptop, and other similar computing devices. The components shown here, their connections and relationships, and their functions, are meant to be exemplary only, and are not meant to limit implementations of the invention described and/or claimed in the present application.

In one embodiment, the computing device 820 includes components such as a processor 860, a system memory 862 having a random access memory (RAM) 864 and a read-only memory (ROM) 866, and a system bus 868 that couples the memory 862 to the processor 860. In another embodiment, the computing device 830 is operable to additionally include components such as a storage device 890 for storing the operating system 892 and one or more application programs 894, a network interface unit 896, and/or an input/output controller 898. Each of the components is operable to be coupled to each other through at least one bus 868. The input/output controller 898 is operable to receive and process input from, or provide output to, a number of other devices 899, including, but not limited to, alphanumeric input devices, mice, electronic styluses, display units, touch screens, signal generation devices (e.g., speakers), or printers.

By way of example, and not limitation, the processor 860 is operable to be a general-purpose microprocessor (e.g., a central processing unit (CPU)), a graphics processing unit (GPU), a microcontroller, a Digital Signal Processor (DSP), an Application Specific Integrated Circuit (ASIC), a Field Programmable Gate Array (FPGA), a Programmable Logic Device (PLD), a controller, a state machine, gated or transistor logic, discrete hardware components, or any other suitable entity or combinations thereof that can perform calculations, process instructions for execution, and/or other manipulations of information.

In another implementation, shown as 840 in FIG. 38 , multiple processors 860 and/or multiple buses 868 are operable to be used, as appropriate, along with multiple memories 862 of multiple types (e.g., a combination of a DSP and a microprocessor, a plurality of microprocessors, one or more microprocessors in conjunction with a DSP core).

Also, multiple computing devices are operable to be connected, with each device providing portions of the necessary operations (e.g., a server bank, a group of blade servers, or a multi-processor system). Alternatively, some steps or methods are operable to be performed by circuitry that is specific to a given function.

According to various embodiments, the computer system 800 is operable to operate in a networked environment using logical connections to local and/or remote computing devices 820, 830, 840 through a network 810. A computing device 830 is operable to connect to a network 810 through a network interface unit 896 connected to a bus 868. Computing devices are operable to communicate communication media through wired networks, direct-wired connections or wirelessly, such as acoustic, RF, or infrared, through an antenna 897 in communication with the network antenna 812 and the network interface unit 896, which are operable to include digital signal processing circuitry when necessary. The network interface unit 896 is operable to provide for communications under various modes or protocols.

In one or more exemplary aspects, the instructions are operable to be implemented in hardware, software, firmware, or any combinations thereof. A computer readable medium is operable to provide volatile or non-volatile storage for one or more sets of instructions, such as operating systems, data structures, program modules, applications, or other data embodying any one or more of the methodologies or functions described herein. The computer readable medium is operable to include the memory 862, the processor 860, and/or the storage media 890 and is operable be a single medium or multiple media (e.g., a centralized or distributed computer system) that store the one or more sets of instructions 900. Non-transitory computer readable media includes all computer readable media, with the sole exception being a transitory, propagating signal per se. The instructions 900 are further operable to be transmitted or received over the network 810 via the network interface unit 896 as communication media, which is

operable to include a modulated data signal such as a carrier wave or other transport mechanism and includes any delivery media. The term “modulated data signal” means a signal that has one or more of its characteristics changed or set in a manner as to encode information in the signal.

Storage devices 890 and memory 862 include, but are not limited to, volatile and non-volatile media such as cache, RAM, ROM, EPROM, EEPROM, FLASH memory, or other solid state memory technology; discs (e.g., digital versatile discs (DVD), HD-DVD, BLU-RAY, compact disc (CD), or CD-ROM) or other optical storage; magnetic cassettes, magnetic tape, magnetic disk storage, floppy disks, or other magnetic storage devices; or any other medium that can be used to store the computer readable instructions and which can be accessed by the computer system 800.

In one embodiment, the computer system 800 is within a cloud-based network. In one embodiment, the server 850 is a designated physical server for distributed computing devices 820, 830, and 840. In one embodiment, the server 850 is a cloud-based server platform. In one embodiment, the cloud-based server platform hosts serverless functions for distributed computing devices 820, 830, and 840.

In another embodiment, the computer system 800 is within an edge computing network. The server 850 is an edge server, and the database 870 is an edge database. The edge server 850 and the edge database 870 are part of an edge computing platform. In one embodiment, the edge server 850 and the edge database 870 are designated to distributed computing devices 820, 830, and 840. In one embodiment, the edge server 850 and the edge database 870 are not designated for distributed computing devices 820, 830, and 840. The distributed computing devices 820, 830, and 840 connect to an edge server in the edge computing network based on proximity, availability, latency, bandwidth, and/or other factors.

It is also contemplated that the computer system 800 is operable to not include all of the components shown in FIG. 38 , is operable to include other components that are not explicitly shown in FIG. 38 , or is operable to utilize an architecture completely different than that shown in FIG. 38 . The various illustrative logical blocks, modules, elements, circuits, and algorithms described in connection with the embodiments disclosed herein are operable to be implemented as electronic hardware, computer software, or combinations of both. To clearly illustrate this interchangeability of hardware and software, various illustrative components, blocks, modules, circuits, and steps have been described above generally in terms of their functionality. Whether such functionality is implemented as hardware or software depends upon the particular application and design constraints imposed on the overall system. Skilled artisans may implement the described functionality in varying ways for each particular application (e.g., arranged in a different order or partitioned in a different way), but such implementation decisions should not be interpreted as causing a departure from the scope of the present invention.

The above-mentioned examples are provided to serve the purpose of clarifying the aspects of the invention, and it will be apparent to one skilled in the art that they do not serve to limit the scope of the invention. By nature, this invention is highly adjustable, customizable and adaptable. The above-mentioned examples are just some of the many configurations that the mentioned components can take on. All modifications and improvements have been deleted herein for the sake of conciseness and readability but are properly within the scope of the present invention. 

The invention claimed is:
 1. An antenna system for detecting metals in an underwater environment, comprising: at least one signal generator, at least one transmitter (Tx) antenna, at least one receiver (Rx) antenna, and at least one signal processor; wherein the at least one Tx antenna and the at least one Rx antenna are fixed in a cross-polarized orientation with each other; wherein the at least one signal generator is operable to emit at least one transmission signal to a target area through the at least one Tx antenna; wherein the at least one transmission signal is an extremely low frequency (ELF) signal; wherein the at least one Rx antenna is operable to receive at least one return signal from the target area; wherein the at least one signal processor is operable to analyze the at least one return signal; wherein the at least one signal processor is operable to detect at least one target object in the target area based on the at least one return signal.
 2. The system of claim 1, further comprising a graphical user interface (GUI), wherein the GUI is operable to display a visualization of the at least one target object in the target area.
 3. The system of claim 1, wherein the at least one Rx antenna is substantially perpendicular to a direction of travel of at least one towing vessel.
 4. The system of claim 1, wherein the at least one transmission signal is a plurality of transmission signals, and wherein the plurality of transmission signals have different frequencies.
 5. The system of claim 1, wherein the at least one signal processor is operable to identify at least one constructive interference zone and at least one destructive interference zone in the target area.
 6. The system of claim 1, wherein the at least one signal processor uses a baseline signal to normalize the at least one return signal.
 7. The system of claim 1, wherein the antenna system is operable to emit at least one additional transmission signal to the target area through the at least one Tx antenna, and wherein an amplitude of the at least one additional transmission signal is based on the at least one return signal.
 8. The system of claim 1, wherein the at least one signal processor is operable to distinguish between different types of metal comprising the at least one target object.
 9. The system of claim 1, wherein the underwater environment is a saltwater environment.
 10. An antenna system for detecting metals in an underwater environment, comprising: at least one signal generator, at least one transmitter (Tx) antenna, at least one receiver (Rx) antenna, and at least one signal processor; and a geolocation system; wherein the at least one Tx antenna and the at least one Rx antenna are fixed in a cross-polarized orientation with each other; wherein the at least one signal generator is operable to emit at least one transmission signal to a target area through the at least one Tx antenna; wherein the at least one transmission signal is an extremely low frequency (ELF) signal; wherein the at least one Rx antenna is operable to receive at least one return signal from the target area; wherein the at least one signal processor is operable to determine a relative geolocation and/or an absolute geolocation of at least one target object using the geolocation system.
 11. The system of claim 10, wherein the geolocation system includes a plurality of signal reflectors in the underwater environment.
 12. The system of claim 10, wherein the underwater environment is a saltwater environment.
 13. The system of claim 10, wherein the geolocation system is located on a floatation device, and wherein the floatation device is connected to at least one towing vessel.
 14. The system of claim 10, wherein the at least one Rx antenna is substantially perpendicular to a direction of travel of at least one towing vessel.
 15. A method for detecting ferrous and non-ferrous metals in an underwater environment, comprising: at least one signal generator emitting at least one transmission signal to the target area through at least one transmitter (Tx) antenna; at least one receiver (Rx) antenna receiving at least one return signal from the target area; at least one signal processor analyzing the at least one return signal; and the at least one signal processor detecting at least one target object in the target area based on the at least one return signal; wherein the at least one transmission signal is an extremely low frequency (ELF) signal; and wherein the at least one Tx antenna and the at least one Rx antenna are fixed in a cross-polarized orientation with each other.
 16. The method of claim 15, wherein the underwater environment is a saltwater environment.
 17. The method of claim 15, wherein the at least one transmission signal is a plurality of transmission signals, wherein the plurality of transmission signals have different frequencies.
 18. The method of claim 15, wherein the at least one Rx antenna is substantially perpendicular to a direction of travel of at least one towing vessel.
 19. The method of claim 15, further comprising the at least one signal processor identifying at least one constructive interference zone and at least one destructive interference zone in the target area.
 20. The method of claim 15, further comprising the at least one signal processor identifying at least one metal comprising the at least one target object. 